Matched filters (Part 2of 2) maximizes the output signal-to-noise ratio for a known radar signal at a predefined time.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://www.solohermelin.com.
10 range and doppler measurements in radar systemsSolo Hermelin
Present method of Range and Doppler measurement in a RADAR system.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://www.solohermelin.com.
Recommend to view this presentation on my website in power point.
Describes Pulse Compression in Radar Systems.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://solohermelin.com.
Since some figures were not downloaded, I recommend to see this presentation on my website under RADAR Folder, Signal Processing subfolder.
Describes Signal Processing in Radar Systems,
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://solohermelin.com.
I recommend to see the presentation on my website under RADAR Folder, Signal Processing Subfolder.
4 matched filters and ambiguity functions for radar signalsSolo Hermelin
Matched filters (Part 1 of 2) maximizes the output signal-to-noise ratio for a known radar signal at a predefined time.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://www.solohermelin.com.
10 range and doppler measurements in radar systemsSolo Hermelin
Present method of Range and Doppler measurement in a RADAR system.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://www.solohermelin.com.
Recommend to view this presentation on my website in power point.
Describes Pulse Compression in Radar Systems.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://solohermelin.com.
Since some figures were not downloaded, I recommend to see this presentation on my website under RADAR Folder, Signal Processing subfolder.
Describes Signal Processing in Radar Systems,
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://solohermelin.com.
I recommend to see the presentation on my website under RADAR Folder, Signal Processing Subfolder.
4 matched filters and ambiguity functions for radar signalsSolo Hermelin
Matched filters (Part 1 of 2) maximizes the output signal-to-noise ratio for a known radar signal at a predefined time.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://www.solohermelin.com.
RADAR - RAdio Detection And Ranging
This is the Part 2 of 2 of RADAR Introduction.
For comments please contact me at solo.hermelin@gmail.com.
For more presentation on different subjects visit my website at http://www.solohermelin.com.
Part of the Figures were not properly downloaded. I recommend viewing the presentation on my website under RADAR Folder.
Tutorial Content
This tutorial provides a broad-based discussion of radar system, covering the following topics:
-Introduction to Radars in Military and Commercial Applications
-Radar System Block Diagram
-Radar Antennas (slotted waveguide array, planar array), Transmitter (magnetron, solid-state), Receiver, Pedestal and Radome
-Plot Extraction, Tracking Algorithms and Display
-Radar Range Equation, Detection Performance
-Wave Propagation and Radar Cross Section
-Emerging and Advanced Radar Systems (phased-array, multi-beam, multi-mode, FMCW, solid-state)
In the discussion, practical systems, technical specifications and data will be used to enhance learning.In addition, simulation results will also be used to present findings.
The objective of the tutorial session is to equip participants with solid understanding of radar systems for system level applications and prepare them for advanced and professional radar courses, projects and research.
This tutorial is designed and developed based on the following references:
[1] G. W. Stimson, Introduction to Airborne Radar Second Edition, Scitech Publishing, 1998.
[2] L. V. Blake, A Guide to Basic Pulse-Radar Maximum-Range Calculation, NRL Report 6930, 1969.
[3] K. H. Lee, Radar Systems for Nanyang Technological University, TBSS, 2014.
Digital Signal Processing[ECEG-3171]-Ch1_L06Rediet Moges
This Digital Signal Processing Lecture material is the property of the author (Rediet M.) . It is not for publication,nor is it to be sold or reproduced.
#Africa#Ethiopia
4 radio wave propagation over the earthSolo Hermelin
Describes the Electromagnetic Wave Propagation over the Earth Surface. Please send comments to solo.hermelin@gmail.com.
For more presentations on different subjects pleade visit my website at http://www,solohermelin.com.
This presentation is in the Radar folder.
Applied Digital Signal Processing 1st Edition Manolakis Solutions Manualtowojixi
Full download http://alibabadownload.com/product/applied-digital-signal-processing-1st-edition-manolakis-solutions-manual/
Applied Digital Signal Processing 1st Edition Manolakis Solutions Manual
RADAR - RAdio Detection And Ranging
This is the Part 1 of 2 of RADAR Introduction.
For comments please contact me at solo.hermelin@gmail.com.
For more presentation on different subjects visit my website at http://www.solohermelin.com.
Part of the Figures were not properly downloaded. I recommend viewing the presentation on my website under RADAR Folder.
Air Combat History describes the main air combats and fighter aircraft, from the beginning of aviation. The additional Youtube links are an important part of the presentation. A list of Air-to-Air Missile from different countries. is also given
For comments please contact me at solo.hermelin@gmail.com.
For more presentations visit my website at http://www.solohermelin.com.
RADAR - RAdio Detection And Ranging
This is the Part 2 of 2 of RADAR Introduction.
For comments please contact me at solo.hermelin@gmail.com.
For more presentation on different subjects visit my website at http://www.solohermelin.com.
Part of the Figures were not properly downloaded. I recommend viewing the presentation on my website under RADAR Folder.
Tutorial Content
This tutorial provides a broad-based discussion of radar system, covering the following topics:
-Introduction to Radars in Military and Commercial Applications
-Radar System Block Diagram
-Radar Antennas (slotted waveguide array, planar array), Transmitter (magnetron, solid-state), Receiver, Pedestal and Radome
-Plot Extraction, Tracking Algorithms and Display
-Radar Range Equation, Detection Performance
-Wave Propagation and Radar Cross Section
-Emerging and Advanced Radar Systems (phased-array, multi-beam, multi-mode, FMCW, solid-state)
In the discussion, practical systems, technical specifications and data will be used to enhance learning.In addition, simulation results will also be used to present findings.
The objective of the tutorial session is to equip participants with solid understanding of radar systems for system level applications and prepare them for advanced and professional radar courses, projects and research.
This tutorial is designed and developed based on the following references:
[1] G. W. Stimson, Introduction to Airborne Radar Second Edition, Scitech Publishing, 1998.
[2] L. V. Blake, A Guide to Basic Pulse-Radar Maximum-Range Calculation, NRL Report 6930, 1969.
[3] K. H. Lee, Radar Systems for Nanyang Technological University, TBSS, 2014.
Digital Signal Processing[ECEG-3171]-Ch1_L06Rediet Moges
This Digital Signal Processing Lecture material is the property of the author (Rediet M.) . It is not for publication,nor is it to be sold or reproduced.
#Africa#Ethiopia
4 radio wave propagation over the earthSolo Hermelin
Describes the Electromagnetic Wave Propagation over the Earth Surface. Please send comments to solo.hermelin@gmail.com.
For more presentations on different subjects pleade visit my website at http://www,solohermelin.com.
This presentation is in the Radar folder.
Applied Digital Signal Processing 1st Edition Manolakis Solutions Manualtowojixi
Full download http://alibabadownload.com/product/applied-digital-signal-processing-1st-edition-manolakis-solutions-manual/
Applied Digital Signal Processing 1st Edition Manolakis Solutions Manual
RADAR - RAdio Detection And Ranging
This is the Part 1 of 2 of RADAR Introduction.
For comments please contact me at solo.hermelin@gmail.com.
For more presentation on different subjects visit my website at http://www.solohermelin.com.
Part of the Figures were not properly downloaded. I recommend viewing the presentation on my website under RADAR Folder.
Air Combat History describes the main air combats and fighter aircraft, from the beginning of aviation. The additional Youtube links are an important part of the presentation. A list of Air-to-Air Missile from different countries. is also given
For comments please contact me at solo.hermelin@gmail.com.
For more presentations visit my website at http://www.solohermelin.com.
Describes Radar Tracking Loops in Range, Doppler and Angles.
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://solohermelin.com.
Estimate the hidden States, Parameters, Signals of a Linear Dynamic Stochastic System from Noisy Measurements. It requires knowledge of probability theory. Presentation at graduate level in math., engineering
For comments please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects visit my website at http://solohermelin.com. Since a few Figure were not downloaded I recommend to see the presentation on my website at RADAR Folder, Tracking subfolder.
This presentation is intended for undergraduate students in physics and engineering.
Please send comments to solo.hermelin@gmail.com.
For more presentations on different subjects please visit my homepage at http://www.solohermelin.com.
This presentation is in the Physics folder.
Introduction to elasticity part 1 of 2 is a presentation at undergraduate in science (physics, mathematics, engineering) level. For comments or improvement suggestions please contact me at solo.hermelin@gmail.com.
For more presentations on different subjects please visit my website at http://www.solohermelin.com.
This presentation is in the Elasticity folder.
Gamma Function mathematics and history.
Please send comments and suggestions for improvements to solo.hermelin@gmail.com. Thanks.
More presentations on different subjects can be found on my website at http://www.solohermelin.com.
Phenomics assisted breeding in crop improvementIshaGoswami9
As the population is increasing and will reach about 9 billion upto 2050. Also due to climate change, it is difficult to meet the food requirement of such a large population. Facing the challenges presented by resource shortages, climate
change, and increasing global population, crop yield and quality need to be improved in a sustainable way over the coming decades. Genetic improvement by breeding is the best way to increase crop productivity. With the rapid progression of functional
genomics, an increasing number of crop genomes have been sequenced and dozens of genes influencing key agronomic traits have been identified. However, current genome sequence information has not been adequately exploited for understanding
the complex characteristics of multiple gene, owing to a lack of crop phenotypic data. Efficient, automatic, and accurate technologies and platforms that can capture phenotypic data that can
be linked to genomics information for crop improvement at all growth stages have become as important as genotyping. Thus,
high-throughput phenotyping has become the major bottleneck restricting crop breeding. Plant phenomics has been defined as the high-throughput, accurate acquisition and analysis of multi-dimensional phenotypes
during crop growing stages at the organism level, including the cell, tissue, organ, individual plant, plot, and field levels. With the rapid development of novel sensors, imaging technology,
and analysis methods, numerous infrastructure platforms have been developed for phenotyping.
DERIVATION OF MODIFIED BERNOULLI EQUATION WITH VISCOUS EFFECTS AND TERMINAL V...Wasswaderrick3
In this book, we use conservation of energy techniques on a fluid element to derive the Modified Bernoulli equation of flow with viscous or friction effects. We derive the general equation of flow/ velocity and then from this we derive the Pouiselle flow equation, the transition flow equation and the turbulent flow equation. In the situations where there are no viscous effects , the equation reduces to the Bernoulli equation. From experimental results, we are able to include other terms in the Bernoulli equation. We also look at cases where pressure gradients exist. We use the Modified Bernoulli equation to derive equations of flow rate for pipes of different cross sectional areas connected together. We also extend our techniques of energy conservation to a sphere falling in a viscous medium under the effect of gravity. We demonstrate Stokes equation of terminal velocity and turbulent flow equation. We look at a way of calculating the time taken for a body to fall in a viscous medium. We also look at the general equation of terminal velocity.
The ability to recreate computational results with minimal effort and actionable metrics provides a solid foundation for scientific research and software development. When people can replicate an analysis at the touch of a button using open-source software, open data, and methods to assess and compare proposals, it significantly eases verification of results, engagement with a diverse range of contributors, and progress. However, we have yet to fully achieve this; there are still many sociotechnical frictions.
Inspired by David Donoho's vision, this talk aims to revisit the three crucial pillars of frictionless reproducibility (data sharing, code sharing, and competitive challenges) with the perspective of deep software variability.
Our observation is that multiple layers — hardware, operating systems, third-party libraries, software versions, input data, compile-time options, and parameters — are subject to variability that exacerbates frictions but is also essential for achieving robust, generalizable results and fostering innovation. I will first review the literature, providing evidence of how the complex variability interactions across these layers affect qualitative and quantitative software properties, thereby complicating the reproduction and replication of scientific studies in various fields.
I will then present some software engineering and AI techniques that can support the strategic exploration of variability spaces. These include the use of abstractions and models (e.g., feature models), sampling strategies (e.g., uniform, random), cost-effective measurements (e.g., incremental build of software configurations), and dimensionality reduction methods (e.g., transfer learning, feature selection, software debloating).
I will finally argue that deep variability is both the problem and solution of frictionless reproducibility, calling the software science community to develop new methods and tools to manage variability and foster reproducibility in software systems.
Exposé invité Journées Nationales du GDR GPL 2024
Earliest Galaxies in the JADES Origins Field: Luminosity Function and Cosmic ...Sérgio Sacani
We characterize the earliest galaxy population in the JADES Origins Field (JOF), the deepest
imaging field observed with JWST. We make use of the ancillary Hubble optical images (5 filters
spanning 0.4−0.9µm) and novel JWST images with 14 filters spanning 0.8−5µm, including 7 mediumband filters, and reaching total exposure times of up to 46 hours per filter. We combine all our data
at > 2.3µm to construct an ultradeep image, reaching as deep as ≈ 31.4 AB mag in the stack and
30.3-31.0 AB mag (5σ, r = 0.1” circular aperture) in individual filters. We measure photometric
redshifts and use robust selection criteria to identify a sample of eight galaxy candidates at redshifts
z = 11.5 − 15. These objects show compact half-light radii of R1/2 ∼ 50 − 200pc, stellar masses of
M⋆ ∼ 107−108M⊙, and star-formation rates of SFR ∼ 0.1−1 M⊙ yr−1
. Our search finds no candidates
at 15 < z < 20, placing upper limits at these redshifts. We develop a forward modeling approach to
infer the properties of the evolving luminosity function without binning in redshift or luminosity that
marginalizes over the photometric redshift uncertainty of our candidate galaxies and incorporates the
impact of non-detections. We find a z = 12 luminosity function in good agreement with prior results,
and that the luminosity function normalization and UV luminosity density decline by a factor of ∼ 2.5
from z = 12 to z = 14. We discuss the possible implications of our results in the context of theoretical
models for evolution of the dark matter halo mass function.
hematic appreciation test is a psychological assessment tool used to measure an individual's appreciation and understanding of specific themes or topics. This test helps to evaluate an individual's ability to connect different ideas and concepts within a given theme, as well as their overall comprehension and interpretation skills. The results of the test can provide valuable insights into an individual's cognitive abilities, creativity, and critical thinking skills
Toxic effects of heavy metals : Lead and Arsenicsanjana502982
Heavy metals are naturally occuring metallic chemical elements that have relatively high density, and are toxic at even low concentrations. All toxic metals are termed as heavy metals irrespective of their atomic mass and density, eg. arsenic, lead, mercury, cadmium, thallium, chromium, etc.
Deep Behavioral Phenotyping in Systems Neuroscience for Functional Atlasing a...Ana Luísa Pinho
Functional Magnetic Resonance Imaging (fMRI) provides means to characterize brain activations in response to behavior. However, cognitive neuroscience has been limited to group-level effects referring to the performance of specific tasks. To obtain the functional profile of elementary cognitive mechanisms, the combination of brain responses to many tasks is required. Yet, to date, both structural atlases and parcellation-based activations do not fully account for cognitive function and still present several limitations. Further, they do not adapt overall to individual characteristics. In this talk, I will give an account of deep-behavioral phenotyping strategies, namely data-driven methods in large task-fMRI datasets, to optimize functional brain-data collection and improve inference of effects-of-interest related to mental processes. Key to this approach is the employment of fast multi-functional paradigms rich on features that can be well parametrized and, consequently, facilitate the creation of psycho-physiological constructs to be modelled with imaging data. Particular emphasis will be given to music stimuli when studying high-order cognitive mechanisms, due to their ecological nature and quality to enable complex behavior compounded by discrete entities. I will also discuss how deep-behavioral phenotyping and individualized models applied to neuroimaging data can better account for the subject-specific organization of domain-general cognitive systems in the human brain. Finally, the accumulation of functional brain signatures brings the possibility to clarify relationships among tasks and create a univocal link between brain systems and mental functions through: (1) the development of ontologies proposing an organization of cognitive processes; and (2) brain-network taxonomies describing functional specialization. To this end, tools to improve commensurability in cognitive science are necessary, such as public repositories, ontology-based platforms and automated meta-analysis tools. I will thus discuss some brain-atlasing resources currently under development, and their applicability in cognitive as well as clinical neuroscience.
Salas, V. (2024) "John of St. Thomas (Poinsot) on the Science of Sacred Theol...Studia Poinsotiana
I Introduction
II Subalternation and Theology
III Theology and Dogmatic Declarations
IV The Mixed Principles of Theology
V Virtual Revelation: The Unity of Theology
VI Theology as a Natural Science
VII Theology’s Certitude
VIII Conclusion
Notes
Bibliography
All the contents are fully attributable to the author, Doctor Victor Salas. Should you wish to get this text republished, get in touch with the author or the editorial committee of the Studia Poinsotiana. Insofar as possible, we will be happy to broker your contact.
Travis Hills' Endeavors in Minnesota: Fostering Environmental and Economic Pr...Travis Hills MN
Travis Hills of Minnesota developed a method to convert waste into high-value dry fertilizer, significantly enriching soil quality. By providing farmers with a valuable resource derived from waste, Travis Hills helps enhance farm profitability while promoting environmental stewardship. Travis Hills' sustainable practices lead to cost savings and increased revenue for farmers by improving resource efficiency and reducing waste.
Seminar of U.V. Spectroscopy by SAMIR PANDASAMIR PANDA
Spectroscopy is a branch of science dealing the study of interaction of electromagnetic radiation with matter.
Ultraviolet-visible spectroscopy refers to absorption spectroscopy or reflect spectroscopy in the UV-VIS spectral region.
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Observation of Io’s Resurfacing via Plume Deposition Using Ground-based Adapt...Sérgio Sacani
Since volcanic activity was first discovered on Io from Voyager images in 1979, changes
on Io’s surface have been monitored from both spacecraft and ground-based telescopes.
Here, we present the highest spatial resolution images of Io ever obtained from a groundbased telescope. These images, acquired by the SHARK-VIS instrument on the Large
Binocular Telescope, show evidence of a major resurfacing event on Io’s trailing hemisphere. When compared to the most recent spacecraft images, the SHARK-VIS images
show that a plume deposit from a powerful eruption at Pillan Patera has covered part
of the long-lived Pele plume deposit. Although this type of resurfacing event may be common on Io, few have been detected due to the rarity of spacecraft visits and the previously low spatial resolution available from Earth-based telescopes. The SHARK-VIS instrument ushers in a new era of high resolution imaging of Io’s surface using adaptive
optics at visible wavelengths.
Professional air quality monitoring systems provide immediate, on-site data for analysis, compliance, and decision-making.
Monitor common gases, weather parameters, particulates.
4 matched filters and ambiguity functions for radar signals-2
1. 1
Matched Filters and
Ambiguity Functions for
RADAR Signals
Part 2
SOLO HERMELIN
Updated: 01.12.08http://www.solohermelin.com
2. 2
SOLO
Matched Filters and Ambiguity Functions for RADAR Signals
Table of Content
RADAR RF Signals
Maximization of Signal-to-Noise Ratio
The Matched Filter
The Matched Filter Approximations
1.Single RF Pulse
2. Linear FM Modulated Pulse (Chirp)
Continuous Linear Systems
Discrete Linear Systems
RADAR Signals
Signal Duration and Bandwidth
Complex Representation of Bandpass Signals
Matched Filter Response to a Band Limited Radar Signal
Matched Filter Response to Phase Coding
Matched Filter Response to its Doppler-Shifted Signal
M
A
T
C
H
E
D
F
I
L
T
E
R
S
3. 3
SOLO
Matched Filters and Ambiguity Functions for RADAR Signals
Table of Content (continue – 1)
Ambiguity Function for RADAR Signals
Definition of Ambiguity Function
Ambiguity Function Properties
Cuts Through the Ambiguity Function
Ambiguity as a Measure of Range and Doppler Resolution
Ambiguity Function Close to Origin
Ambiguity Function for Single RF Pulse
Ambiguity Function for Linear FM Modulation Pulse
Ambiguity Function for a Coherent Pulse Train
Ambiguity Function Examples (Rihaczek, A.W.,
“Principles of High Resolution Radar”)
References
5. 5
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Definition of Ambiguity Function:
( ) ( ) ( ) ( ) ( ) ( )[ ]
( ) ( )[ ]tjta
tjttatsjtstg QI
θ
θθ
exp
sincos:
=
+=+=
• Ambiguity Function is an analytic tool for investigating the effect of target motion
on the matching filter response.
• It is a function of waveform only.
• It can be used to characterize:
- Range Resolution
- Doppler Resolution
- Range – Doppler coupling
- Loses due to mismatched Doppler
Ambiguity Function for RADAR Signals
Return to Table of Content
12. 12
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Definition of Ambiguity Function:
Cuts Through the Ambiguity Function
( ) ( ) ( ) ( )τττ ggD RdttgtgfX =−== ∫
+∞
∞−
∗
0,Cut through the delay axis:
where Rgg (τ) is the autocorrelation function of the signal envelope.
The cut along the Ambiguity Function
along the delay axis is the shape of the
“range window” at zero Doppler. This is
how the envelope of the Matched Filter
will look as a function of time.
Linear FM pulse
Single pulse
13. 13
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Definition of Ambiguity Function:
Cuts Through the Ambiguity Function (continue – 1)
Cut through the frequency axis:
This is the Fourier Transform of signal envelope energy, and the cut at τ = 0 is
independent of any phase or frequency modulation and is determined only by the
magnitude of the complex envelope of the signal – that is by amplitude modulation.
( ) ( ) ( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
∗
=== dttfjtgdttfjtgtgfX DDD ππτ 2exp2exp,0
2
( )DfX ,0=τ( ) 2
tg
F
F-1
Return to Table of Content
14. 14
Ambiguity Function for RADAR SignalsSOLO
Ambiguity as a Measure of Range and Doppler Resolution
Suppose that the transmitted signal s (t) is returned by two targets whose signals s1 (t)
and s2 (t) differ only in range (delay time τ) and Doppler (frequency fD).
The Resolution of the Radar is related to how it can distinguish between the two
signals. A tractable criteria of resolution is the integrated square difference
magnitude, denoted by |ε|2
, and defined by
( ) ( ) tfj
etgts 02
: π
=
( ) ( ) ( ) ( )[ ] ( ) ( )[ ] ( ) ( ) ( ) ( )[ ] ( ) ( )[ ]{ }∫∫∫
+∞
∞−
+∞
∞−
+∞
∞−
−−+=−−=−= dttstststststsdttstststsdttsts 2121
2
2
2
12121
2
21
2
****ε
In order to obtain a difference in delay and Doppler we will define the complex signals:
( ) ( ) ( ) ( ) ( )[ ] ( )[ ] ( )[ ]
( ) ( ) ( )[ ] ( )[ ] ( )[ ]∫
∫∫∫
∞+
∞−
+∞
∞−
+∞
∞−
+∞
∞−
−−−−−−−
−−−−−−−−−+=
dttfjtfjfjtgtg
dttfjtfjfjtgtgdttgdttg
DD
DD
221121021
221121021
222
2exp2exp2exp*
2exp2exp2exp*
τπτπττπττ
τπτπττπτττε
Note: The real signals are ( ) ( ) ( )[ ] ( ) ( ) ( )[ ] 2/*&2/* 222111 tstststststs +=+=
( ) ( ) ( ) ( )
( ) ( ) ( ) ( )
−=
−=
−+
−+
220
110
2
22
2
11
:
:
τπ
τπ
τ
τ
tffj
tffj
D
D
etgts
etgts
- Transmitted signal
- Received signals
17. 17
Ambiguity Function for RADAR SignalsSOLO
Ambiguity as a Measure of Range and Doppler Resolution (continue – 3)
( ) ( ) ( )
( )
( )[ ] ( ){ }
( )
( )
( )[ ] ( ){ }DD
tgofEnergy
DD
tgofEnergy
fXffjdttg
fXffjdttgdttsts
∆∆−∆+−−=
∆−∆∆+−=−=
∫
∫∫
∞+
∞−
+∞
∞−
+∞
∞−
,2expRe22
,2expRe22
20
2
10
22
21
2
ττπ
ττπε
2121 :&: DDD fff −=∆−=∆ τττDefine
Good Resolution requires that |ε|2
be large for any delay Δτ ≠0 and Doppler ΔfD ≠0.
The first term is the energies (positive) of the complex envelopes of the two signals.
The second term has a minus sign, hence |ε|2
will be increased when the second term
will decrease.
( )[ ] ( ){ } ( ) ( )[ ] ( ){ }( )DDDDD fXffjfXfXffj ∆∆∆+−∆∆=∆∆∆+− ,2expargcos,,2expRe 2020 ττπτττπ
Good resolution is obtained when (Ambiguity Function) is minimum for
non-zero target delay Δτ and Doppler ΔfD.
( )DfX ∆∆ ,τ
( ) ( ) ( ) ( )
( ) ( ) ( ) ( )
−=
−=
−+
−+
220
110
2
22
2
11
:
:
τπ
τπ
τ
τ
tffj
tffj
D
D
etgts
etgts
Received complex signal
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,where ( ) ( ) ( )DDD fXfjfX −−=− ,*2exp, ττπτ
18. 18
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
∗
==−== fdfjfGfGRdttgtgfX ggD τπτττ 2exp*:0,
SOLO
Ambiguity as a Measure of Range and Doppler Resolution (continue – 4)
Range Resolution
( )
( ) 2
2
0,0
0,
:
X
dfX
T
D
res
∫
+∞
∞−
=
=
ττ
Assume the two signals have the same Doppler fD = 0. The range resolution is defined as:
( ) ( ) ( ) ( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
∗
−=−= fdfjfGffGtdtfjtgtgfX DDD τππττ 2exp*2exp:,
Using
we have
( )τggR -1
F
F ( ) 2
fG
( ) ( ) ( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
∗
====== fdfGfGRdttgtgfX ggD *0:0,0 ττ
( )
( )
( )
( )
2
2
4
2
2
0
==
∫
∫∫
∞+
∞−
+∞
∞−
+∞
∞−
fdfG
fdfG
R
dR
T
gg
gg
res
ττ
Parseval’s Theoremand
19. 19
Ambiguity Function for RADAR SignalsSOLO
Ambiguity as a Measure of Range and Doppler Resolution (continue – 5)
Doppler Resolution
( )
( ) 2
2
0,0
,0
:
X
fdfX
F
DD
res
∫
+∞
∞−
=
=
τ
Assume the two signals have the same range delay τ = 0. The Doppler resolution
is defined as:
( ) ( ) ( ) ( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
∗
−=−= fdfjfGffGtdtfjtgtgfX DDD τππττ 2exp*2exp:,
Using
we have
( ) 2
tg -1
F
F ( )DGG fR
( ) ( ) ( ) ( ) ( ) ( ) ( )0*0:0,0 ====== ∫∫
+∞
∞−
+∞
∞−
∗
fRfdfGfGRdttgtgX GGgg τ
( )
( )
( )
( )
2
2
4
2
2
0
==
∫
∫∫
∞+
∞−
+∞
∞−
+∞
∞−
tdtg
tdtg
R
fdfR
F
GG
GG
res
Parseval’s Theoremand
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )DGGDGGDDD fRfRfdfGffGtdtfjtgtgfX =−=−=== ∫∫
+∞
∞−
+∞
∞−
∗
*2exp:,0 πτ
20. 20
Ambiguity Function for RADAR SignalsSOLO
Ambiguity as a Measure of Range and Doppler Resolution (continue – 6)
Range – Doppler Resolution
( )
( )
( )
( )
2
2
4
2
2
0
==
∫
∫∫
∞+
∞−
+∞
∞−
+∞
∞−
tdtg
tdtg
R
fdfR
F
GG
GG
res
( )
( )
( )
( )
2
2
4
2
2
0
==
∫
∫∫
∞+
∞−
+∞
∞−
+∞
∞−
fdfG
fdfG
R
dR
T
gg
gg
res
ττ
From Schwarz Inequality: ( ) ( ) ( ) ( )∫∫∫
+∞
∞−
+∞
∞−
+∞
∞−
≤ dtthdttfdtthtf
22
Choose ( ) ( ) ( ) ( ) ( )tg
td
tgd
thtgttf ':& ===
( ) ( ) ( ) ( )∫∫∫
+∞
∞−
+∞
∞−
+∞
∞−
≤ dttsdttstdttstst
22
''we obtain
21. 21
Ambiguity Function for RADAR SignalsSOLO
Ambiguity as a Measure of Range and Doppler Resolution (continue – 7)
Good resolution is obtained when (Ambiguity Function) is minimum for
non-zero target delay τ and Doppler fD.
( )DfX ,τ
A waveform has an Ideal Ambiguity Function if it has a “Thumbtack” shape:
• No response unless the echo is closely matched to the Doppler for which the filter
is designed.
• And a very narrow peak in range, yielding good range resolution.
Can’t get rid of the pedestal because of the “constant volume” property.
Return to Table of Content
22. 22
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Ambiguity Function Close to Origin
( ) ( ) ( ) ( ) DfD
D
fDD ffX
f
fXXfX DD 0
02
0
0222
,,0,0, =
=
=
=
∂
∂
+
∂
∂
+= ττ
τττ
τ
τ
Let develop the Square of the Ambiguity Function in a Taylor series around the
origin τ=0, fD=0
Since |X (0,0)|2
is the maximum of the continuous |X (τ,fD)|2
we must have
( ) ( ) 0,, 0
02
0
02
=
∂
∂
=
∂
∂
=
=
=
=
DD fD
D
fD fX
f
fX ττ
ττ
τ
( ) ( ) ( ) +
∂
∂
+
∂
∂
∂
∂
+
∂
∂
+ =
=
=
=
=
= 2
0
02
2
2
0
022
0
02
2
2
,,2,
2
1
DfD
D
DfD
D
fD ffX
f
ffX
f
fX DDD
τττ
τττ
τ
ττ
τ
( ) ( ) ( ) ( ) ( )
( ) ( ) ( ) ( )
( )
( ) ( ) ( ) ( )
( )
∫ ∫∫ ∫
∫ ∫
∞+
∞−
∞+
∞−
∗
∞+
∞−
∞+
∞−
∗
+∞
∞−
+∞
∞−
∗
=
−−
∂
∂
+−−
∂
∂
=
−−
∂
∂
=
∂
∂
ττ
ττ
τ
ττ
τ
ττ
τ
τ
τ
gggg
D
RR
fD
dttgtgdttgtgdttgtgdttgtg
dtdttgtgtgtgfX
111222
*
222111
2122110
2
**
*,
also
( ) ( ) ( ) ( ) ( ) ( ) ( )
( )
00*0,
000
0
02
=
∂
∂
=
∂
∂
+
∂
∂
=
∂
∂
=≠
+∞
∞−
+∞
∞−
∗
≠
=
=
∫∫
τ
τ
τ
τ
τ
τ
gg
gggg
f
D
R
Rdttg
t
tgdttg
t
tgRfX D
23. 23
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
( ) ( ) ( ) ( ) ( ) ( ) ,2,1,0,,2,1,0*
2
*
==
−
=− ∫∫
+∞
∞−
+∞
∞−
mnd
d
Sd
S
j
dt
td
tsd
tstj m
m
n
n
n
n
mm
ω
ω
ω
ωω
π
SOLO
Ambiguity Function Close to Origin (continue – 1)
( ) ( ) ( ) ( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
∗
= −
∂
∂
+−
∂
∂
=
∂
∂
ττ
τ
ττ
τ
τ
τ
ggggfD RdttgtgRdttgtgfX D 2221110
2
**,
( ) ( ) ( ) ( ) ( ) ( )
( )
( ) ( ) ( ) ( ) ( )
( )
∫∫
∫∫
∞+
∞−
∞+
∞−
+∞
∞−
∗
+∞
∞−
∗
=
∂
∂
−
∂
∂
+−
∂
∂
+
∂
∂
−
∂
∂
+−
∂
∂
=
∂
∂
τ
τ
τ
τ
ττ
τ
τ
τ
τ
τ
ττ
τ
τ
τ
gg
gg
gg
ggfD
R
dttgtgRdttgtg
R
dttgtgRdttgtgfX D
222222
2
2
111112
2
10
2
2
2
**
*
*,
Since is a maximum for τ=0, we have( ) ( ) sgggg ERR 20*0 ==
( ) ( )
0
0*0
=
∂
=∂
=
∂
=∂
τ
τ
τ
τ gggg RR
( ) ( ) ( ) ( ) ( ) ( )
∂
∂
+
∂
∂
=
∂
∂
∫∫
+∞
∞−
+∞
∞−
∗
=
=
dttgtgdttgtgRfX
s
D
E
gg
f
D 2
2
2
2
2
0
02
2
2
*0,
ττ
τ
τ
τ
n=2
m=0
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )[ ] ( )
sE
ggss
f
s
Parseval
dffGffEdffGfEdGG
E
2
222222
2
2
222:2222*
2
22
∫∫∫
+∞
∞−
+∞
∞−
=+∞
∞−
+∆−=−=−= πππωωωω
π
πω
Relationship
from Parseval’s
Theory
24. 24
Signal Duration and BandwidthSOLO
( )tf
-1
F
F
( )ωFRelationships from Parseval’s Formula
( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
= ωωω
π
dFFdttftf 2
*
12
*
1
2
1
Parseval’s Formula7
Choose ( ) ( ) ( ) ( )tstjtftf
m
−== 21
( ) ( ) ,2,1,0
2
1
2
22
== ∫∫
∞+
∞−
∞+
∞−
nd
d
Sd
dttst m
m
m
ω
ω
ω
π
( ) ( )tftj
n
−
-1
F
F ( )ω
ω
F
d
d
n
n
and use 5a
Choose ( ) ( ) ( )
n
n
td
tsd
tftf == 21 and use 5b
( )tf
td
d
n
n
-1
F
F
( ) ( )ωω Fj
n
( ) ( ) ,2,1,0
2
1 22
2
== ∫∫
∞+
∞−
∞+
∞−
ndSdt
td
tsd m
n
n
ωωω
π
Choose or the oppositec
( ) ( ) ( ) ( ) ( ) ( ) ,2,1,0,,2,1,0
2
*
*
==
= ∫∫
∞+
∞−
∞+
∞−
mnd
d
Sd
S
j
dt
td
tsd
tstj m
m
n
n
n
n
mm
ω
ω
ω
ωω
π
( ) ( )
n
n
td
tsd
tf =1
( ) ( ) ( )tstjtf
m
−=2
( ) ( ) ( ) ( ) ( ) ( ) ,2,1,0,,2,1,0*
2
*
==
−
=− ∫∫
+∞
∞−
+∞
∞−
mnd
d
Sd
S
j
dt
td
tsd
tstj m
m
n
n
n
n
mm
ω
ω
ω
ωω
π
c1
c2
25. 25
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
( ) ( ) ( )[ ]222
0
02
2
2
22, ggsfD ffEfX D
+∆−=
∂
∂
=
=τ
τ
τ
( )
( ) ( ) ( )
( )∫
∫
∞+
∞−
+∞
∞−
−
=∆
dffG
dffGff
f
g
g
2
222
2
2
22
:
π
ππ
SOLO
Ambiguity Function Close to Origin (continue -2)
We found:
where:
Δfg – is signal envelope bandwidth
Es – is signal energy ( ) ( ) ( )∫∫∫
+∞
∞−
+∞
∞−
+∞
∞−
=== tdtgfdfGtdtsEs
222
2
1
2
2
1
: π
fg – is signal envelope frequency median
( ) ( )
( )∫
∫
∞+
∞−
+∞
∞−
=
dffG
dffGf
fg
2
2
2
22
:
π
ππ
( )
( ) ( )
( )∫
∫
∞+
∞−
+∞
∞−
=+∆
dffG
dffGf
ff gg
2
222
22
2
22
π
ππ
26. 26
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Ambiguity Function Close to Origin (continue -3)
In the same way:
( ) ( ) ( ) ( ) ( ) ( )[ ]
( ) ( ) ( ) ( )[ ]∫ ∫
∫ ∫
∞+
∞−
∞+
∞−
+∞
∞−
+∞
∞−
∗∗
−−=
−
∂
∂
=
∂
∂
2121
2
2
2
121
21212211
2
2exp2
2exp,0
dtdtttfjtgtgttj
dtdtttfjtgtgtgtg
f
fX
f
D
D
D
D
D
ππ
π
Since |X (0,0)|2
is the maximum of the continuous |X (τ,fD)|2
we must have
( ) ( ) ( ) ( )
( ) ( ) ( ) ( ) 022
2,
21
1
2
12
2
222
2
21
2
11
21
2
2
2
121
0
0
2
≡−=
−=
∂
∂
⇔
∞+
∞−
∞+
∞−
∞+
∞−
∞+
∞−
+∞
∞−
+∞
∞−=
=
∫ ∫∫ ∫
∫ ∫
tt
f
D
D
dttgdttgtjdttgdttgtj
dtdttgtgttjfX
f D
ππ
πτ
τ
29. 29
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Ambiguity Function Close to Origin (continue -6)
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )[ ] ( ) ( )
( ) ( ) ( ) ( ) ( ) gs fEdffGfGf
dGGdGGGGdttg
t
tgtg
t
tgj
22222*22
*2****2
22
ππππ
ωωωωωωωωωωωπ
==
=+=
∂
∂
−
∂
∂
∫
∫∫∫
∞+
∞−
+∞
∞−
+∞
∞−
+∞
∞−
( ) ( ) sEdttgtg 2* =∫
+∞
∞−
( ) ( ) ( )
( )
( )
( ) gs tE
dttg
dttgt
dttgdttgtgt 2*
2
2
2
==
∫
∫
∫∫ ∞+
∞−
+∞
∞−
∞+
∞−
∞+
∞−
( ) ( ) ( ) ( ) ( ) ( ) ,2,1,0,,2,1,0
2
*
*
==
= ∫∫
∞+
∞−
∞+
∞−
mnd
d
Sd
S
j
dt
td
tsd
tstj m
m
n
n
n
n
mm
ω
ω
ω
ωω
π
( ) ( ) ( ) ( ) ( ) ( ) ,2,1,0,,2,1,0*
2
*
==
−
=− ∫∫
+∞
∞−
+∞
∞−
mnd
d
Sd
S
j
dt
td
tsd
tstj m
m
n
n
n
n
mm
ω
ω
ω
ωω
π
c1
c2
Relationships
from Parseval’s
Theorem
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )
∫∫
+∞
∞−
+∞
∞−
−
−=
∂
∂
−
∂
∂
− ω
ω
ω
ω
ω
ω
ωωπ d
d
Sd
S
d
Sd
Sjdttg
t
tgttg
t
tgtj
*
***2
( ) ( ) ( ) ( ) ( ) ( ) ( ) ggss
f
D
D
ftEdttg
t
tgtEfX
f D
22
0
0
2
2
222*Im222,0 ππ
τ
τ
+
∂
∂
=
∂∂
∂
∫
+∞
∞−=
=
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )∫∫∫ ∫
+∞
∞−
+∞
∞−
+∞
∞−
+∞
∞−=
=
∂
∂
−
∂
∂
−
∂
∂
−
∂
∂
+=
∂∂
∂
dttg
t
tgtg
t
tgdttgtgtjdttg
t
tgtg
t
tgtdttgtgjfX
f Df
D
D
***2***2,0
0
0
2
2
ππ
τ
τ
30. 30
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Ambiguity Function Close to Origin (continue -7)
( ) ( ) ( ) ( ) ( ) +
∂
∂
+
∂∂
∂
+
∂
∂
+=
=
=
=
=
=
=
2
0
0
2
2
2
0
0
2
2
2
0
0
2
2
2
22
,
2
1
,,
2
1
0,0, D
f
D
D
D
f
D
Df
DD ffX
f
ffX
f
fXXfX
DDD
τττ
τττ
τ
ττ
τ
τ
( ) ( ) ( )[ ]( ) ( ) ( ) ( ) ( ) ( ) ( )
( ) ( ) +∆−
+
∂
∂
++∆−= ∫
+∞
∞−
2222
22222222
22
222*Im22222,
Dgs
DggsssggsD
ftE
fftEdttg
t
tgtEEffEfX
π
τππττ
( )
( )
( )[ ] ( )
( )
( ) ( ) ( ) ( ) ( ) +∆−
+
∂
∂
++∆−= ∫
∞+
∞−
222222
2
2
222*Im
2
2
21
0,0
,
DgDggs
s
gg
D
ftfftEdttg
t
tgt
E
ff
X
fX
πτπ
π
τ
τ
If we choose the time and frequency origins such that
( )
( )
( ) ( )
( )
0
2
22
:&0:
2
2
2
2
====
∫
∫
∫
∫
∞+
∞−
+∞
∞−
∞+
∞−
+∞
∞−
dffG
dffGf
f
dttg
dttgt
t gg
π
ππ
( )
( )
( ) ( )
( )
( ) ( ) ( ) +∆−
∂
∂
+∆−= ∫
∞+
∞−
=
=
22222
0
0
2
2
2*Im
2
2
21
0,0
,
DgD
s
g
t
f
D
ftfdttg
t
tgt
E
f
X
fX
g
g
πτ
π
τ
τ
31. 31
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Ambiguity Function Close to Origin (continue -8)
( )
( )
( ) ( )
( )
( ) ( ) ( ) +∆−
∂
∂
+∆−= ∫
∞+
∞−
=
=
22222
0
0
2
2
2*Im
2
2
21
0,0
,
DgD
s
g
t
f
D
ftfdttg
t
tgt
E
f
X
fX
g
g
πτ
π
τ
τ
Helstrom’s Uncertainty Ellipse
The curve resulting from the interception of a plane parallel to the τ, fD plane and the
Normalized Ambiguity Function is an ellipse. The ellipse computed when the plane is at
a height of 0.75 is referred to as Helstrom’s Uncertainty Ellipse.
( )
( )
( ) ( )
( )
( ) ( ) ( )
4
3
2*Im
2
2
21
0,0
, 22222
0
0
2
2
=+∆−
∂
∂
+∆−= ∫
∞+
∞−
=
=
DgD
s
g
t
f
D
ftfdttg
t
tgt
E
f
X
fX
g
g
πτ
π
τ
τ
( ) ( )
( )
( ) ( ) ( )
4
1
2*Im
2
2
2
22222
=∆+
∂
∂
−∆ ∫
+∞
∞−
DgD
s
g ftfdttg
t
tgt
E
f πτ
π
τ
32. 32
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Ambiguity Function Close to Origin (continue -4)
( ) ( ) ( ) ( ) ( ) ( ) ( )
∫∫ ∫
+∞
∞−
+∞
∞−
+∞
∞−
−=
∂
∂
− ω
ω
ω
ωωπ d
d
Gd
GEjdttgtgdttg
t
tgtj s *2**2 22211
1
11
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )
∫∫∫ ∫
+∞
∞−
+∞
∞−
+∞
∞−
+∞
∞−
−
=
∂
∂
+ ω
ω
ω
ωωωωω
π
π d
d
Gd
GdGG
j
dttgtgtdttg
t
tgj
*
222211
1
1 *
2
**2
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )∫∫∫ ∫
+∞
∞−
+∞
∞−
+∞
∞−
+∞
∞−
=
∂
∂
− ωωωω
π
ω
ω
ω
ωπ dGG
j
d
d
Gd
Gdttg
t
tgdttgtgtj *
2
***2 22
2
21111
( ) ( ) ( ) ( ) ( ) ( ) ( )
∫∫ ∫
+∞
∞−
+∞
∞−
+∞
∞−
=
∂
∂
+ ω
ω
ω
ωωπ d
d
Gd
GEjdttg
t
tgtdttgtgj s
*
22
2
22111 2**2
c2 m=n=1
c2 m=0
n=1
c1
m=1
n=0
c2 m=1
n=0
c1
m=0
n=1
c1 m=n=1
( ) ( ) ( ) ( ) ( ) ( )
( ) ( ) ( ) ( ) ( ) ( )
∫∫
∫
∞+
∞−
∞+
∞−
∞+
∞−=
=
−
−
−
=
∂∂
∂
ω
ω
ω
ω
ω
ω
ωωωωω
π
ω
ω
ω
ω
ω
ω
ωω
τ
τ
d
d
Gd
G
d
Gd
GjdGG
d
d
Gd
G
d
Gd
GjEfX
f
s
f
D
D D
**
2
1
*2,0
*
*
0
0
2
2
( ) ( ) ( ) ( ) ( ) ( ) ,2,1,0,,2,1,0
2
*
*
==
= ∫∫
∞+
∞−
∞+
∞−
mnd
d
Sd
S
j
dt
td
tsd
tstj m
m
n
n
n
n
mm
ω
ω
ω
ωω
π
( ) ( ) ( ) ( ) ( ) ( ) ,2,1,0,,2,1,0*
2
*
==
−
=− ∫∫
+∞
∞−
+∞
∞−
mnd
d
Sd
S
j
dt
td
tsd
tstj m
m
n
n
n
n
mm
ω
ω
ω
ωω
π
c1
c2
Relationships
from Parseval’s
Theorem
33. 33
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
( ) ( ) ( )
s
D
E
g
f
D dffGffX
2
22
0
0
2
2
22, ∫
+∞
∞−
=
= ∆−=
∂
∂
πτ
τ
τ
( )
( ) ( )
( )∫
∫
∞+
∞−
+∞
∞−
=∆
dffG
dffGf
fg
2
222
2
2
22
:
π
ππ
SOLO
Ambiguity Function Close to Origin (continue -1)
( ) ( ) ( ) ( ) ( ) ( ) ( )
s
D
E
g
f
D
D
dttgtgtdttgtgtfX
f
2
222
0
0
2
2
22, ∫∫
+∞
∞−
∗
+∞
∞−
∗
=
= ∆−=−=
∂
∂
ππτ τ
We found:
where:
Δfg – is signal envelope bandwidth
Es – is signal energy ( ) ( ) ( )∫∫∫
+∞
∞−
+∞
∞−
+∞
∞−
=== tdtgfdfGtdtsEs
222
2
1
2
2
1
: π
or ( ) ( ) ( ) ( )
s
D
E
g
f
D
D
dttgtgtfX
f
2
2
0
0
2
2
2, ∫
+∞
∞−
∗
=
= ∆−=
∂
∂
πτ τ
Δtg – is signal envelope duration ( )
( )
( )∫
∫
∞+
∞−
+∞
∞−
=∆
tdtg
tdtgt
tg
2
22
2
:
34. 34
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( )∫
+∞
∞−
∗
−= dttfjtgtgfX DD πττ 2exp:,
SOLO
Ambiguity Function Close to Origin (continue -2)
( ) ( ) ( ) ( ) ( ) ( ) ( )
∂
∂
=
−
∂
∂
=
∂
∂
∂
∂
=
∂
∂
∂
∂
∫∫
+∞
∞−
∗
+∞
∞−
∗
=
=
=
= dttg
t
tgtdttfjtgtgtjfX
f
fX
f
DfD
D
f
D
D
DD
ππτ
τ
πτ
τ
τ
τ
ττ 2Im2exp2Re,Re, 0
0
0
0
Define
( ) ( )
( ) ( )
( )
( ) ( )
∂
∂
∆∆
−=
∂
∂
∆∆
−= ∫
∫
∫ ∞+
∞−
∗
∞+
∞−
∗
+∞
∞−
∗
dttg
t
tgt
Eft
dttgtg
dttg
t
tgt
ft sgggg 2
1
Im
1
:ρ
Error Coupling
Coefficient
We obtain
( ) ( ) ( ) ( ) ggs
f
D
D
ftEdttg
t
tgtfX
f D
∆∆−=
∂
∂
=
∂
∂
∂
∂
∫
+∞
∞−
∗
=
= ρππτ
τ
τ 222Im,
0
0
35. 35
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for Single RF Pulse
( )
( )
>
≤≤−
=
2/0
2/2/cos 0
p
pp
SPi
tt
ttttA
ts
ω
The complex envelope is
( )
>
≤≤−
=
2/0
2/2/
1
p
pp
pSP
tt
ttt
ttg
( ) ( ) ( ) ( )
( )
( )
( )
( )
( )
( )
( )
( )
( )
( )
<
<
=
<
<
=−= ++
−
+
+−
+
−
+
+−
∞+
∞−
∗
∫
∫
∫
02exp
2
1
02exp
2
1
02exp
1
02exp
1
2exp:, 2/
2/
2/
2/
2/
2/
2/
2/
τπ
π
τπ
π
τπ
τπ
πττ τ
τ
τ
τ
p
p
p
p
p
p
p
p
t
t
D
pD
t
t
D
pD
t
t
D
p
t
t
D
p
DDSP
tfj
tfj
tfj
tfj
tdtfj
t
tdtfj
t
tdtfjtgtgfX
<
+
−−
+
<
−
−−
−
=
<
−−
+
<
+−−
=
0
2
2
2exp
2
2exp
0
2
2
2exp
2
2exp
2
2exp
0
2
2
2exp
2
2exp
0
2
2
2exp
2
2exp
τ
π
τ
π
τ
π
τ
π
τ
τ
π
τ
π
τ
π
τ
π
πτπ
τ
π
τππ
pD
p
D
p
D
pD
p
D
p
D
D
pD
p
D
p
D
pD
p
D
p
D
tfj
t
fj
t
fj
tfj
t
fj
t
fj
fj
tfj
t
fj
t
fj
tfj
t
fj
t
fj
36. 36
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for Single RF Pulse (continue – 1)
( ) ( )
( )[ ] ( ) ( ) ( )[ ]
( ) p
ppD
ppD
pD
pD
pD
DDSP t
ttf
ttf
tfj
tf
tf
fjfX ≤
−
−
−=
−
= τ
τπ
τπ
ττπ
π
τπ
τπτ
/1
/1sin
/1exp
sin
exp,
Therefore:
( )
( ) ( )[ ]
( )
≤
−
−
−
=
elsewere
t
ttf
ttf
t
fX
p
ppD
ppD
p
DSP
0
/1
/1sin
/1
,
τ
τπ
τπ
τ
τ
( ) ( ) ppSP ttX ≤−= τττ /10,
( )
[ ]
pD
pD
DSP
tf
tf
fX
π
πsin
,0 =
37. 37
Ambiguity Function for RADAR Signals
( )
( )
p
t
p
t
pSP
DSP
res t
t
d
tX
dfX
T
pp
=
−=
−=
=
= ∫
∫
+∞
∞−
0
2
0
2
2
2
212
0,0
0,
:
τ
ττ
τ
ττ
( )
( )
( )
( )
p
t
p
SP
SP
SP
DDSP
res
t
td
t
tdtg
tdtg
X
fdfX
F
p
12
0,0
,0
:
2/
0
2
1
2
2
4
1
2
2
==
=
=
= ∫
∫
∫∫
∞+
∞−
+∞
∞−
+∞
∞−
τ
( )
>
≤≤−
=
2/0
2/2/
1
p
pp
pSP
tt
ttt
ttg
SOLO
Ambiguity Function for Single RF Pulse (continue – 2)
( )
( ) ( )[ ]
( )
≤
−
−
−
=
elsewere
t
ttf
ttf
t
fX
p
ppD
ppD
p
DSP
0
/1
/1sin
/1
,
τ
τπ
τπ
τ
τ
( ) ( ) ppSP ttX ≤−= τττ /10,
Range Resolution
( ) 10,0 =SPX
Doppler Resolution
p
resres
t
FV
22
λλ
==
Return to Table of Content
38. 38
Ambiguity Function for RADAR Signals
( ) ( ) ( ) ( ) ( ) ( ) ( ) ( )[ ] ( )∫∫
+∞
∞−
∗
+∞
∞−
∗
−−−=−= tdtfjtkjtgtkjtgtdtfjtgtgfX DSPSPDFMSPFMSPDFMSP πτπτππττ 2expexpexp2exp:,
22
SOLO
Ambiguity Function for Linear FM Modulation Pulse
( )
>
≤
+
=
2
0
22
cos
2
0
τ
τπ
ω
t
t
tk
tA
ts FMSPi
( )
[ ]
( ) [ ]2
2
exp
2
0
2
exp
1
tkjtg
t
t
t
ttkj
t
tg SP
p
p
p
FMSP π
π
=
>
≤
=
The signal
of Single Pulse
Frequency Modulated
The complex envelope
of Single Pulse
Frequency Modulated
( )tgSP
- the complex envelope of Single RF Pulse
( ) ( ) ( ) ( ) ( )[ ] ( ) ( )τττπτπττπτ kfXkjtdtkfjtgtgkjfX DSPDSPSPDFMSP +−=+−−= ∫
+∞
∞−
∗
,exp2expexp, 22
( ) ( ) ( )[ ]
( ) p
ppD
ppD
pDSP t
ttf
ttf
tfX ≤
−
−
−= τ
τπ
τπ
ττ
/1
/1sin
/1,where Ambiguity Function of the Single
Frequency Pulse
( )
( ) ( ) ( )[ ]
( ) ( )
≤
−+
−+
−
=
elsewere
t
ttkf
ttkf
t
fX
p
ppD
ppD
p
DFMSP
0
/1
/1sin
/1
,
τ
ττπ
ττπ
τ
τ
39. 39
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for Linear FM Modulation Pulse (continue – 1)
( )
( ) ( ) ( )[ ]
( ) ( )
( )ττ
τ
ττπ
ττπ
τ
τ
kfX
elsewere
t
ttkf
ttkf
t
fX
DSP
p
ppD
ppD
p
DFMSP
+=
≤
−+
−+
−
=
,
0
/1
/1sin
/1
,
40. 40
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for Linear FM Modulation Pulse (continue – 2)
( )
( ) ( ) ( )[ ]
( ) ( )
( )ττ
τ
ττπ
ττπ
τ
τ
kfX
elsewere
t
ttkf
ttkf
t
fX
DSP
p
ppD
ppD
p
DFMSP
+=
≤
−+
−+
−
=
,
0
/1
/1sin
/1
,
( ) ( )
( )0,
,,
τ
τττττ
SP
SPFMSP
X
kkXkX
=
+−=−
41. 41
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for Linear FM Modulation Pulse (continue – 3)
( )
( )
( )
p
p
p
p
p
p
DFMSP t
t
tk
t
tk
t
fX ≤
−
−
−== τ
τ
τπ
τ
τπ
τ
τ
1
1sin
10,
tp
τ1’st null
( ) π
τ
τπ =
−
p
p
t
tk 1
p
tk
pp
nullst
tkk
tt p
11
42
42
'1
2
>>
≈−−=τ
k tp = Δf is the total frequency
deviation during the pulse.
p
nullst
p
p
tk
nullst tf
t
DrationCompressio
ftk
p
∆===
∆
=≈
>>
'1
4
'1
11
2
τ
τ
Return to Table of Content
42. 42
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for a Coherent Pulse Train
The envelope of each pulse is of unit energy and the
coherence is maintained from pulse to pulse.
( ) ( ) ( ) ( ) ( ) ( ) ( )
( ) ( ) ( )∑ ∑ ∫
∫∑ ∑∫
−
=
−
=
∞+
∞−
+∞
∞−
−
=
−
=
+∞
∞−
−−−=
−−−=−=
1
0
1
0
1
0
1
0
*
2exp*
1
2exp*
1
2exp,
N
n
N
m
DRSPRSP
D
N
n
N
m
RSPRSPDPTPTDPT
tdtfjTmtgTntg
N
tdtfjTmtgTntg
N
tdtfjtgtgfX
πτ
πτπττ
( ) ( ) ( ) ( )[ ] ( )∑ ∑ ∫
−
=
−
=
+∞
∞−
−=
−−−=
1
0
1
0
1111 2exp*2exp
1
,
1 N
n
N
m
DRSPSPRD
Tntt
DPT tdtfjTnmtgtgTnfj
N
fX
R
πτπτ
( ) [ ] ( ) ( )
( ) ( )[ ]
( ) ( )
≤
−
−
−
==−∫
∞+
∞−
elsewere
tfj
ttf
ttf
t
fXtdtfjtgtg
pD
ppD
ppD
p
DSPDSPSP
0
2exp
/1
/1sin
/1
,2exp* 1111
ττπ
τπ
τπ
τ
τπτ
( )
>
≤≤−
=
2/0
2/2/
1
p
pp
pSP
tt
ttt
ttg Envelope of
Single Pulse
( ) ( )∑
−
=
−=
1
0
1 N
n
RSPPT Tntg
N
tg
Envelope of a
Pulse Train
( ) ( ) ( ){ }tfjtgts PT 02expRe π= Pulse Train Signal
For a Coherent Pulse Train:
where for a Single Pulse, we found:
implies coherency
43. 43
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for a Coherent Pulse Train
(continue – 1)
( ) ( ) ( )∑ ∑
−
=
−
=
−=−=
1
0
1
0
:,2exp
1
,
N
n
N
m
DRSPRDDPT mnpfTpXTnfj
N
fX τπτ
For a Coherent Pulse Train:
Construction Table for the
Double Sum with p=n-m
n
m 0 1 2 … N-1
0 0 1 2 … N-1
1 -1 0 1 … N-2
2 -2 -1 0 … N-3
… … … … … …
N-1 -N-1 -N-2 -N-3 … 0
p=n-m
( )
BlockTriangularRight
pmn
N
p
pN
m
DiagonalBlockTriangularLow
pnm
Np
pN
n
N
n
N
m
+=
−
=
−−
=
−=
−−=
−−
=
−
=
−
=
∑ ∑∑ ∑∑ ∑ +=
1
1
1
0
&
0
1
1
0
1
0
1
0
( ) ( ) ( )
( )
( ) ( ) ( )∑ ∑
∑ ∑
−
=
−−
=
−−=
−−
=
−+
−=
1
1
1
1
0
1
1
0
2exp,2exp
1
2exp,
1
,
N
p
pN
m
RDDRSPRD
Np
pN
n
RDDRSPDPT
TmfjfTpXTpfj
N
TnfjfTpX
N
fX
πτπ
πττ
44. 44
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for a Coherent Pulse Train
(continue – 2)
For a Coherent Pulse Train:
( ) ( ) ( )
( )
( ) ( ) ( )∑ ∑
∑ ∑
−
=
−−
=
−−=
−−
=
−+
−=
1
1
1
0
0
1
1
0
2exp,2exp
1
2exp,
1
,
N
p
pN
m
RDDRSPRD
Np
pN
n
RDDRSPDPT
TmfjfTpXTpfj
N
TnfjfTpX
N
fX
πτπ
πττ
To compute the sums of the exponents, we use:
( ) ( ) ( )
2/12/1
2/2/
2/1
2/1
0 1
1
yy
yy
y
y
y
y
y
pNpNpNpNpN
n
n
−
−
=
−
−
= −
−−−−−−−
=
∑
take: ( )RD Tfjy π2exp=
( ) ( )[ ] ( )[ ]
( )RD
RD
RD
pN
n
RD
Tf
TpNf
TpNfjTnfj
π
π
ππ
sin
sin
1exp2exp
1
0
−
−−=∑
−−
=
Using this result we obtain:
( ) ( )[ ] ( )
( )[ ]
( )( )
∑
−
−−=
−
−+−=
1
1 sin
sin
,1exp
1
,
N
Np RD
RD
DRSPRDDPT
Tf
TpNf
fTpXTpNfj
N
fX
π
π
τπτ
45. 45
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for a Coherent Pulse Train
(continue – 3)
For a Coherent Pulse Train:
( ) ( )[ ] ( )
( )[ ]
( )( )
∑
−
−−=
−
−+−=
1
1 sin
sin
,1exp
1
,
N
Np RD
RD
DRSPRDDPT
Tf
TpNf
fTpXTpNfj
N
fX
π
π
τπτ
where
The expression |XPT (τ,fD)| can be simplified if the separation between pulses is larger
than the duration of individual pulses.
( ) ( )
( )[ ]
( )( )
( ) ( )[ ]
( )
( )[ ]
( )( )
2/
sin
sin
/1
/1sin
/1
1
sin
sin
,
1
,
1
1
1
1
Rp
N
Np RD
RD
pRpD
pRpD
pR
N
Np RD
RD
DRSPDPT
Tt
Tf
TpNf
tTptf
tTptf
tTp
N
Tf
TpNf
fTpX
N
fX
<
−
−−
−−
−−=
−
−=
∑
∑
−
−−=
−
−−=
π
π
τπ
τπ
τ
π
π
ττ
( )
( ) ( )[ ]
( ) ( )
≤
−
−
−
=
elsewere
tfj
ttf
ttf
t
fX
pD
ppD
ppD
p
DSP
0
2exp
/1
/1sin
/1
,
ττπ
τπ
τπ
τ
τ
46. 46
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for a Coherent Pulse Train
(continue – 4)
The Ambiguity Function for a Coherent Pulse Train:
Setting fD = 0 we obtain:
( ) ( ) ( )[ ]
( )
( )[ ]
( )( )
2/
sin
sin
/1
/1sin
/1
1
,
1
1
Rp
N
Np RD
RD
pRpD
pRpD
pRDPT Tt
Tf
TpNf
tTptf
tTptf
tTp
N
fX <
−
−−
−−
−−= ∑
−
−−= π
π
τπ
τπ
ττ
( )
( )[ ]
( )( ) ( )
( )pN
Tf
Tf
TpNf
TpNf
t
Tp
N
fX
DD
fRD
RD
N
Np
fRD
RD
p
R
DPT −
−
−
−
−=
=
−
−−=
=
∑
1
0
1
1
1
0
sin
sin
1
1
,
π
π
π
πτ
τ
( )
( )
pR
N
Np p
R
DPT tTp
N
p
t
Tp
fX <−
−
−
−== ∑
−
−−=
τ
τ
τ 110,
1
1
or
47. 47
Ambiguity Function for RADAR SignalsSOLO
Ambiguity Function for a Coherent Pulse Train
(continue – 5)
The Ambiguity Function for a Coherent Pulse Train:
( )
( ) ( )[ ]
( )
( )[ ]
( )( )
2/
sin
sin
/1
/1sin
/1
1
,
1
1
Rp
N
Np RD
RD
pRpD
pRpD
pR
DPT
Tt
Tf
TpNf
tTptf
tTptf
tTp
N
fX
<
−
−−
−−
−−= ∑
−
−−= π
π
τπ
τπ
τ
τ
48. 48
Pulse bi-phase Barker coded of length 7
Digital Correlation
At the Receiver the coded pulse enters a
7 cells delay lane (from left to right),
a bin at each clock.
The signals in the cells are multiplied
by ck* and summed.
clock
-1 = -11
+1 -1 = 02
-1 +1 -1 = -13
-1 -1 +1-( -1) = 04
+1 -1 -1 –(+1)-( -1) = -15
+1 +1 -1-(-1) –(+1)-1= 06
+1+1 +1-( -1)-(-1) +1-(-1)= 77
+1+1 –(+1)-( -1) -1-( +1)= 08
+1-(+1) –(+1) -1-( -1)= -19
-(+1)-(+1) +1 -( -1)= 010
-(+1)+1-(+1) = -111
+1-(+1) = 012
-(+1) = -1
13
0 = 014
SOLO Pulse Compression Techniques
-1-1 -1+1+1+1+1 { }*
kc
65. 65
Ambiguity function for a square pulse
Ambiguity function for an LFM pulse Return to Table of Content
66. 66
Matched Filters for RADAR SignalsSOLO
References
J.V.DiFranco, W.I. Rubin, “RADAR Detection”, Artech House, 1981, Ch.5, pp.143-201
C.E. Cook, M. Bernfeld, “RADAR Signals An Introduction to Theory and Application”,
Artech House, 1993
D. C. Schleher, “MTI and Pulsed Doppler RADAR”, Artech House, 1991, Appendix B
J. Minkoff, “Signals, Noise, and Active Sensors”, John Wiley & Sons, 1992, Ch.5
M.A. Richards, ECE 6272, “Fundamentals of Signal Processing”, Georgia Institute of
Technology, Spring 2000, Appendix A, Optimum and Sub-optimum Filters
W.B. Davenport,Jr., W.L. Root,”An Introduction to the Theory of Random Signals
and Noise”, McGraw Hill, 1958, pp. 244-246
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, Ch.5 & 6
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998
N. Levanon, “Waveform Analysis and Design”, 2008 IEEE Radar Conference,
Tutorial, MA2, May 26 – 30, 2008, Rome, Italy
Hermelin, S., “Pulse Compression Techniques”, Power Point Presentation
Return to Table of Content
67. January 19, 2015 67
SOLO
Technion
Israeli Institute of Technology
1964 – 1968 BSc EE
1968 – 1971 MSc EE
Israeli Air Force
1970 – 1974
RAFAEL
Israeli Armament Development Authority
1974 –2013
Stanford University
1983 – 1986 PhD AA
Vector Analysis
68. 68
Fourier Transform
( ) ( ){ } ( ) ( )∫
+∞
∞−
−== dttjtftfF ωω exp:F
SOLO
Jean Baptiste Joseph
Fourier
1768-1830
F (ω) is known as Fourier Integral or Fourier Transform
and is in general complex
( ) ( ) ( ) ( ) ( )[ ]ωφωωωω jAFjFF expImRe =+=
Using the identities
( ) ( )t
d
tj δ
π
ω
ω =∫
+∞
∞− 2
exp
we can find the Inverse Fourier Transform ( ) ( ){ }ωFtf -1
F=
( ) ( ) ( ) ( ) ( )
( ) ( )( ) ( ) ( ) ( ) ( )[ ]00
2
1
2
exp
2
expexp
2
exp
++−=−=−=
−=
∫∫ ∫
∫ ∫∫
∞+
∞−
∞+
∞−
∞+
∞−
+∞
∞−
+∞
∞−
+∞
∞−
tftfdtfd
d
tjf
d
tjdjf
d
tjF
ττδττ
π
ω
τωτ
π
ω
ωττωτ
π
ω
ωω
( ) ( ){ } ( ) ( )∫
+∞
∞−
==
π
ω
ωωω
2
exp:
d
tjFFtf -1
F
( ) ( ) ( ) ( )[ ]00
2
1
++−=−∫
+∞
∞−
tftfdtf ττδτ
If f (t) is continuous at t, i.e. f (t-0) = f (t+0)
This is true if (sufficient not necessary)
f (t) and f ’ (t) are piecewise continue in every finite interval1
2 and converge, i.e. f (t) is absolute integrable in (-∞,∞)( )∫
+∞
∞−
dttf
69. 69
( )atf −
-1
F
F ( ) ( )ωω ajF −exp
Fourier TransformSOLO
( )tf
-1
F
F
( )ωFProperties of Fourier Transform (Summary)
Linearity1
( ) ( ){ } ( ) ( )[ ] ( ) ( ) ( )ωαωαωαααα 221122112211 exp: FFdttjtftftftf +=−+=+ ∫
+∞
∞−
F
Symmetry2
( )tF
-1
F
F
( )ωπ −f2
Conjugate Functions3 ( )tf *
-1
F
F
( )ω−*
F
Scaling4 ( )taf
-1
F
F
a
F
a
ω1
Derivatives5 ( ) ( )tftj
n
−
-1
F
F ( )ω
ω
F
d
d
n
n
( )tf
td
d
n
n
-1
F
F
( ) ( )ωω Fj
n
Convolution6
( ) ( )tftf 21
-1
F
F ( ) ( )ωω 21
* FF( ) ( ) ( ) ( )∫
+∞
∞−
−= τττ dtfftftf 2121
:*
-1
F
F ( ) ( )ωω 21
FF
( ) ( ) ( ) ( )∫∫
+∞
∞−
+∞
∞−
= ωωω dFFdttftf 2
*
12
*
1
Parseval’s Formula7
Shifting: for any a real8
( ) ( )tajtf exp
-1
F
F ( )aF −ω
Modulation9 ( ) ttf 0
cos ω -1
F
F
( ) ( )[ ]00
2
1
ωωωω −++ FF
( ) ( ) ( ) ( ) ( ) ( )∫∫∫
+∞
∞−
+∞
∞−
+∞
∞−
−=−= ωωω
π
ωωω
π
dFFdFFdttftf 212121
2
1
2
1
70. 70
Fourier Transform
( )tf
( ) ( )∑
∞
=
−=
0n
T Tntt δδ
( ) ( ) ( ) ( ) ( )∑
∞
=
−==
0
*
n
T
TntTnfttftf δδ
( )tf *
( )tf
T t
( ) ( ){ } ( ) σσ <== +∫
∞
−
f
ts
dtetftfsF
0
L
SOLO
Sampling and z-Transform
( ) ( ){ } ( ) σδδ <
−
==
−== −
∞
=
−
∞
=
∑∑ 0
1
1
00
sT
n
sTn
n
T
e
eTnttsS LL
( ) ( ){ }
( ) ( ) ( )
( ) ( ){ } ( ) ( )
<<
−
=
=
−
==
−
∞+
∞−
−−
∞
=
−
∞
=
+∫
∑∑
0
00
**
1
1
2
1
σσσξξ
π
δ
δ
ξ
σ
σ
ξ f
j
j
tsT
n
sTn
n
d
e
F
j
ttf
eTnfTntTnf
tfsF
L
L
L
( )
( ) ( )
( )
( )
( )
( )
( )
( )
( )
( )
( )
( )
−
=
−
−
=
−
=
∑∫
∑∫
∑
−−
−
−−
Γ
−−
−−
Γ
−−
∞
=
−
ts
e
ofPoles
tsts
F
ofPoles
tsts
n
nsT
e
F
Resd
e
F
j
e
F
Resd
e
F
j
eTnf
sF
ξ
ξξ
ξ
ξξ
ξ
ξ
ξ
π
ξ
ξ
ξ
π
1
1
0
*
112
1
112
1
2
1
Poles of
( ) Ts
e ξ−−
−1
1
Poles of
( )ξF
planes
T
nsn
π
ξ
2
+=
ωj
ωσ j+
0=s
Laplace Transforms
The signal f (t) is sampled at a time period T.
1Γ
2
Γ
∞→R
∞→R
Poles of
( ) Ts
e ξ−−
−1
1
Poles of
( )ξF
planeξ
T
nsn
π
ξ
2
+=
ωj
ωσ j+
0=s
71. 71
Fourier Transform
( )tf
( ) ( )∑
∞
=
−=
0n
T Tntt δδ
( ) ( ) ( ) ( ) ( )∑
∞
=
−==
0
*
n
T
TntTnfttftf δδ
( )tf *
( )tf
T t
SOLO
Sampling and z-Transform (continue – 1)
( ) ( )
( )
( )
( )
( ) ( ) ∑∑
∑∑
∞+
−∞=
∞+
−∞=
−−→
∞+
−∞=
−−
+→
+=
−
−−
+=
−
+
−=
+
−
−−
−=
−
−=
−−
−−
nn
Tse
n
ts
T
n
js
T
n
js
e
ofPoles
ts
T
n
jsF
TeT
T
n
jsF
T
n
jsF
e
T
n
js
e
F
RessF
ts
n
ts
π
π
π
π
ξ
ξ
ξ
ξπ
ξ
π
ξ
ξ
ξ
ξ
21
2
lim
2
1
2
lim
1
1
2
2
1
1
*
Poles of
( )ξF
ωj
σ
0=s
T
π2
T
π2
T
π2
Poles of
( )ξ*
F plane
js ωσ +=
The signal f (t) is sampled at a time period T.
The poles of are given by( )ts
e ξ−−
−1
1
( )
( )
T
n
jsnjTsee n
njTs π
ξπξπξ 2
21 2
+=⇒=−−⇒==−−
( ) ∑
+∞
−∞=
+=
n T
n
jsF
T
sF
π21*
72. 72
Fourier Transform
( )tf
( ) ( )∑
∞
=
−=
0n
T Tntt δδ
( ) ( ) ( ) ( ) ( )∑
∞
=
−==
0
*
n
T
TntTnfttftf δδ
( )tf *
( )tf
T t
SOLO
Sampling and z-Transform (continue – 2)
0=z
planez
Poles of
( )zF
C
The signal f (t) is sampled at a time period T.
The z-Transform is defined as:
( ){ } ( ) ( )
( )
( ) ( )
( )
−
−===
∑
∑
=
−
→
∞
=
−
=
iF
iF
i
iF
Ts
FofPoles
T
F
n
n
ze
ze
F
zTnf
zFsFtf
ξξ
ξ
ξ
ξξ
ξξξ
1
0
*
1
lim:Z
( )
( )
<
>≥
= ∫
−
00
0
2
1 1
n
RzndzzzF
jTnf
fC
C
n
π
73. 73
Fourier TransformSOLO
Sampling and z-Transform (continue – 3)
( ) ( ) ( )∑∑
∞
=
−
+∞
−∞=
=
+=
0
* 21
n
nsT
n
eTnf
T
n
jsF
T
sF
πWe found
The δ (t) function we have:
( ) 1=∫
+∞
∞−
dttδ ( ) ( ) ( )τδτ fdtttf =−∫
+∞
∞−
The following series is a periodic function: ( ) ( )∑ −=
n
Tnttd δ:
therefore it can be developed in a Fourier series:
( ) ( ) ∑∑
−=−=
n
n
n T
tn
jCTnttd πδ 2exp:
where: ( )
T
dt
T
tn
jt
T
C
T
T
n
1
2exp
1
2/
2/
=
= ∫
+
−
πδ
Therefore we obtain the following identity:
( )∑∑ −=
−
nn
TntT
T
tn
j δπ2exp
Second Way
74. 74
Fourier Transform
( ) ( ){ } ( ) ( )∫
+∞
∞−
−== dttjtftfF νπνπ 2exp:2 F
( ) ( ) ( )∑∑
∞
=
−
+∞
−∞=
=
+=
0
* 21
n
nsT
n
eTnf
T
n
jsF
T
sF
π
( ) ( ){ } ( ) ( )∫
+∞
∞−
== ννπνπνπ dtjFFtf 2exp2:2-1
F
SOLO
Sampling and z-Transform (continue – 4)
We found
Using the definition of the Fourier Transform and it’s inverse:
we obtain ( ) ( ) ( )∫
+∞
∞−
= ννπνπ dTnjFTnf 2exp2
( ) ( ) ( ) ( ) ( ) ( )∑∫∑
∞
=
+∞
∞−
∞
=
−=−=
0
111
0
*
exp2exp2exp
nn
n
sTndTnjFsTTnfsF ννπνπ
( ) ( ) ( )[ ]∫ ∑
+∞
∞−
+∞
−∞=
−−== 111
*
2exp22 νννπνπνπ dTnjFjsF
n
( ) ( ) ∑∫ ∑
+∞
−∞=
+∞
∞−
+∞
−∞=
−=
−−==
nn T
n
F
T
d
T
n
T
FjsF νπνννδνπνπ 2
11
22 111
*
We recovered (with –n instead of n) ( ) ∑
+∞
−∞=
+=
n T
n
jsF
T
sF
π21*
Second Way (continue)
Making use of the identity: with 1/T instead of T
and ν - ν 1 instead of t we obtain: ( )[ ] ∑∑
−−=−−
nn T
n
T
Tnj 11
1
2exp ννδννπ
( )∑∑ −=
−
nn
TntT
T
tn
j δπ2exp
75. 75
Fourier TransformSOLO
Henry Nyquist
1889 - 1976
http://en.wikipedia.org/wiki/Harry_Nyquist
Nyquist-Shannon Sampling Theorem
Claude Elwood Shannon
1916 – 2001
http://en.wikipedia.org/wiki/Claude_E._Shannon
The sampling theorem was implied by the work of Harry Nyquist in
1928 ("Certain topics in telegraph transmission theory"), in which
he showed that up to 2B independent pulse samples could be sent
through a system of bandwidth B; but he did not explicitly consider
the problem of sampling and reconstruction of continuous signals.
About the same time, Karl Küpfmüller showed a similar result, and
discussed the sinc-function impulse response of a band-limiting
filter, via its integral, the step response Integralsinus; this band-
limiting and reconstruction filter that is so central to the sampling
theorem is sometimes referred to as a Küpfmüller filter (but seldom
so in English).
The sampling theorem, essentially a dual of Nyquist's result,
was proved by Claude E. Shannon in 1949 ("Communication in
the presence of noise"). V. A. Kotelnikov published similar
results in 1933 ("On the transmission capacity of the 'ether' and
of cables in electrical communications", translation from the
Russian), as did the mathematician E. T. Whittaker in 1915
("Expansions of the Interpolation-Theory", "Theorie der
Kardinalfunktionen"), J. M. Whittaker in 1935 ("Interpolatory
function theory"), and Gabor in 1946 ("Theory of
communication").
http://en.wikipedia.org/wiki/Nyquist-Shannon_sampling_theorem
76. 76
SignalsSOLO
Signal Duration and Bandwidth
then
( ) ( )∫
+∞
∞−
−
= tdetsfS tfi π2
( ) ( )∫
+∞
∞−
= fdefSts tfi π2
t
t∆2
t
( ) 2
ts
f
f
f∆2
( ) 2
fS
( ) ( )
( )
2/1
2
22
:
−
=∆
∫
∫
∞+
∞−
+∞
∞−
tdts
tdtstt
t
( )
( )∫
∫
∞+
∞−
+∞
∞−
=
tdts
tdtst
t
2
2
:
Signal Duration Signal Median
( ) ( )
( )
2/1
2
22
2
4
:
−
=∆
∫
∫
∞+
∞−
+∞
∞−
fdfS
fdfSff
f
π ( )
( )∫
∫
∞+
∞−
+∞
∞−
=
fdfS
fdfSf
f
2
2
2
:
π
Signal Bandwidth Frequency Median
Fourier
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
http://en.wikipedia.org/wiki/Ambiguity_function
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Richards, M.E., ECE 6272, “Fundamentals of Radar Signal Processing”, Spring 2000, Georgiatech
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, “Radar Resolution”, pp.355 - 375
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, “Radar Resolution”, pp.355 - 375
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, “Radar Resolution”, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.117-118
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Brookner, E., Ed., “Radar Technology”, Artech House, 1982, Ch.7, Sinsky,”Waveform Selection and Processing”
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
Cook, C.E., Bernfeld, M., “Radar Signals – An Introduction to Theory and Application”, Artech House, 1993, pp.80-83
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.129-132
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.129-132
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.129-132
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
N. Levanon, “Radar Principles”, John Wiley & Sons, 1988, pp.132-136
Peeble, P.Z. Jr, “Radar Principles”, John Wiley & Sons, 1998, Ch. 8, Radar Resolution, pp.355 - 375
Levanon, N., “Waveform Analysis and Design”, 2008 IEEE Radar Conference, May 26 – 30, Rome, Italy
Minkoff, J., “Signals, Noise, and Active Sensors”, John Wiley & Sons, 1992, pp.72-74
François Le Chevalier, “Principes De Traitement Des Signaux Radar et Sonar”, Masson, 1989, pp.39 et 75
Ralph Deutsch, “System Analysis Techniques”, Prentice-Hall, Inc., 1969, § 4.7, “Effective Bandwidth”, pp.126-138
Athanasios Papoulis, “signal Analysis”, McGraw-Hill, 1977, § 8-2, Uncertainty Principle and Sophisticated Signals,
pp.273-278
Minkoff, J., “Signals, Noise, and Active Sensors”, John Wiley & Sons, 1992, pp.72-74
François Le Chevalier, “Principes De Traitement Des Signaux Radar et Sonar”, Masson, 1989, pp.39 et 75
Minkoff, J., “Signals, Noise, and Active Sensors”, John Wiley & Sons, 1992, pp.72-74
François Le Chevalier, “Principes De Traitement Des Signaux Radar et Sonar”, Masson, 1989, pp.39 et 75
Ralph Deutsch, “System Analysis Techniques”, Prentice-Hall, Inc., 1969, § 4.7, “Effective Bandwidth”, pp.126-138
Minkoff, J., “Signals, Noise, and Active Sensors”, John Wiley & Sons, 1992, pp.72-74
François Le Chevalier, “Principes De Traitement Des Signaux Radar et Sonar”, Masson, 1989, pp.39 et 75
Minkoff, J., “Signals, Noise, and Active Sensors”, John Wiley & Sons, 1992, pp.72-74
François Le Chevalier, “Principes De Traitement Des Signaux Radar et Sonar”, Masson, 1989, pp.39 et 75