1. Infinite Impulse Response (IIR) Filter
Supervised:
Prof .Dr. Bayan Mahdi Sabbar AL-Ibrahimy
Prepare by:
Fatimah Azeez
Al Nahrain University
College of Information Engineering
Department of Network Engineering
2. Contents
Introduction to IIR Filter
Structures for IIR Systems
Direct-Form Structures
Signal –Flow Graphs and Transposed Structures
Cascade-Form Structures
Parallel-Form Structures
Lattice and Lattice-Ladder Structures for IIR Systems
IIR Filter Design
IIR Filter Design by Approximation of Derivatives
IIR Filter Design by Impulse Invariance
IIR Filter Design by the Bilinear Transformation
Characteristics of Commonly Used Analog Filters
Butterworth
Chebyshev
Elliptic filters
Bessel filters
Frequency Transformations
Frequency Transformations in Analog Domain
Frequency Transformations in Digital Domain
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3. Filter Design is Everywhere
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• Multimedia & Biomedical
Electronics
Noise Cancellation, Audio
Compression, Speech recognition,
Hearing Aids, EKG
• Communications
Cellular Phone , Cable, GPS,
Wireless Broadcast, WiFi
• Medical & Computer Vision
Process Control, Robotics,
Autonomous Navigation, Tracking
• Safety & Security Systems
Biometric access & control, Driver
awareness system
3
4. Recursive or Infinite Impulse Response
(IIR) Filters
A recursive filter has feedback from output to input, and in general its output is a
function of the previous output samples and the present and past input samples as
described by the following equation:
Thus are recursive filter is also known as an Infinite Duration Impulse
Response(IIR) filter.
Other names for an IIR filter include feedback filters, pole-zero filters and auto-
regressive-moving-average (ARMA) filter a term usually used in statistical signal
processing literature.
Where and are filter coefficients
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IIR Transfer Function:
5. Comparison FIR vs IIR
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vs
01
An FIR filter is less compact in
that it can usually achieve a
prescribed frequency response
with a smaller number of
coefficients
An IIR filter is more compact in
that it can usually achieve a
prescribed frequency response
with a smaller number of
coefficients
01
vs
02
FIR filters are less
efficient in memory
and computational
requirements
IIR filters are more
efficient in memory and
computational
requirements
02
vs
03
FIR filter is always
stable
An IIR filter unstable 03
vs
04
FIR can be designed
to be Linear Phase
filter or Non-Linear
Phase
IIR filter have Non-
Linear Phase
04
7. Structure for IIR System
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1. Direct – Form Structures
2. Signal –Flow Graphs and Transposed Structures
3. Cascade – Form Structures
4. Parallel– Form Structures
5. Lattice and Lattice – Ladder Structures for IIR Systems
8. Direct – Form Structures
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• The System Function That characterizes an IIR System can
be viewed as form cascade , that is,
– Where 𝐻1(𝑧) consists Zeros of H(z)
Or 𝐻1(𝑧) is the transfer function of a feed-forward, all-zero, filter
given by
– H2(z): consists Poles of H(z)
Or H2(z): is the transfer function of a feed back, all-pole,
recursive filter given by
9. Direct – Form I Structures
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Requires M+N+1 memory locations,
M+N+1 multiplies, M+N Additions
10. Direct – Form II Structures
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Delayed versions of the sequence
{w(n)} Consequently, only single set
of memory locations is required for
storing the past values of {w(n)}
Requires
{M,N} memory locations
M+N+1 multiplies
M+N Additions
11. Signal –Flow Graphs and Transposed
Structures
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12. Signal –Flow Graphs and Transposed
Structures
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1& 3
summing
nodes
2, 4,& 5
branching
points
13. Transposed direct form II Structures
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1-reverse all
signal flow
directions
2-Change
nodes into
adders and
adders into
nodes
3-Interchange
i/p & o/p
14. Signal –Flow Graphs and Transposed
Structures
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The transposed direct form II realization that we
have obtained can be described by the set of
difference equations
Requires
Same No. of
memory locations
multiplies
Additions
16. Cascade – Form Structures
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(N>=M) The System can be factored into a cascade of second-
order subsystems, such that H(z) can be expressed as
Where K is the integer part of (N+1)/2.
Hk(z) has the general form
The coefficients and in the second-order
subsystems are real.
17. Cascade – Form Structures
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Quadratic factor any
two real valued zeros
can be paired
together
Quadratic factor in
numerator consist of
either a pair of real roots
or pair of complex –
conjugate roots
18. Parallel Filter Structure
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Obtained by performing a partial fraction expansion of H(z).
we obtain the result
Where {Pk} are the poles & {Ak} are the coefficients in the
partial-fraction expansion
the constant C is defined as C=bN/aN.
To avoid multiplications by complex
numbers, we can combine pairs of
complex-conjugate poles to form two-pole
subsystem
19. Parallel Filter Structure (Cont.)
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Where the coefficients {bki} and {aki}
are real-valued system parameters.
The overall function can now be
expressed as
Where K : integer part of (N+1)/2.
when N is odd, one of the Hk(z) is
really a single-pole system (i.e.,
bk1=ak2=0)
20. Example 3: Parallel Structure of IIR
Filter
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Example Determine the cascade and parallel realizations for
the system described by the system function
Solution: the cascade realization is easily obtained from this
form. One possible pairing of poles and zeros is
21. Example 3: Parallel Structure of IIR
Filter
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The cascade realization
To obtain the parallel-form, H(Z) must be expanded in partial functions
22. Example 3: Parallel Structure of IIR
Filter
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The parallel-form realization
23. Example 3: Parallel Structure of IIR
Filter
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A1=2.93,
A2=-17.68,
A3= 12.25-j14.57
A*3=12.25+j14.57
24. Lattice and Lattice – Ladder Structures
for IIR Systems
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25. Lattice and Lattice – Ladder Structures
for IIR Systems
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26. Lattice and Lattice – Ladder Structures
for IIR Systems
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27. Lattice and Lattice – Ladder Structures
for IIR Systems
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28. Lattice and Lattice – Ladder Structures
for IIR Systems
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29. Design of IIR filter
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30. Design IIR Filters from Analog Filter
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Analog filter can be described by its systems functions
Where {αk} and {βk} are the filters coefficient,
impulse response which is related to Ha(s) by the Laplace transform
The analog filter having the relation system function H(s) can be
described by the linear constant-coefficient differential equation
Where x(t): input signal
y(x):output of filter signal
We begin design of digital filter in analog
domain (S-plane) and then convert the
design into digital domain (Z-plane)
31. Design IIR Filters from Analog Filter
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32. Design IIR Filters from Analog Filter
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Passband
edge
frequency
Stopband edge
frequency
Peak ripple
value
Peak ripple value
Transition band
33. Design IIR Filters from Analog Filter
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34. IIR Filter Design by Approximation of
Derivative
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1- j𝜴 𝒂𝒙𝒊𝒔 𝒊𝒏 𝒕𝒉𝒆 𝒔
− 𝒑𝒍𝒂𝒏𝒆 𝒔𝒉𝒐𝒖𝒍𝒅 𝒎𝒂𝒑 𝒊𝒏𝒕𝒐 𝒕𝒉𝒆 𝒖𝒏𝒊𝒕
𝒄𝒊𝒓𝒄𝒍𝒆 𝒊𝒏 𝒕𝒉𝒆 𝒛 − 𝒑𝒍𝒂𝒏𝒆
2-The left-half plane (LHP) of the S-
plane should map into the inside
of the unit circle in the Z-plane
35. IIR Filter Design by Approximation of
Derivative
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36. IIR Filter Design by Approximation of
Derivative
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37. Example of IIR Filter Design by
Approximation of Derivative
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38. IIR Filter Design by Impulse Invariance
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39. IIR Filter Design by Impulse Invariance
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40. IIR Filter Design by Impulse Invariance
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41. IIR Filter Design by Impulse Invariance
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42. Example: IIR Filter Design by Impulse
Invariance
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43. Example: IIR Filter Design by Impulse
Invariance
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44. IIR Filter Design by Bilinear Transform
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The mapping from the s-plane to the z-plane (thus avoiding
aliasing of frequency components ) is
Ω
This Method overcomes the limitation of
other two design methods (appropriate only
for lowpass filters and a limited class of
bandpass filters)
45. IIR Filter Design by Bilinear Transform
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46. Example- IIR Filter Design by Bilinear
Transform
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47. Example- IIR Filter Design by Bilinear
Transform
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48. IIR Filter Design by Bilinear Transform
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49. IIR Filter Design by Bilinear Transform
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79. IIR Filter Design by Bilinear Transform
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For LPF and HPF:
For BPF and BRF:
Frequency Warping
Prototype
Transformation
Obtained digital filter Transfer
Function:
From
analog LPF
to desired
analog filter
82. Example 1: Bilinear Transformation
Method
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82
Design a first-order high-pass digital Chebyshev filter with a
cut-off frequency of 3 kHz and 1 dB ripple on the pass-band
using a sampling frequency of 8,000 Hz.
Probl
em:
Solution:
Digital frequency
(rad/s):
Pre-warped analog
frequency :
First-order LP Chebyshev filter
prototype:
Applying transformation
LPF to HPF:
Dividing by 1.9625
Applying
BLT:
83. Example 2: Bilinear Transformation
Method
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Problem:
Solution:
Design a second-order digital band-pass Butterworth filter with the
following specifications:
Digital frequencies:
pre-warped analog
frequency:
A first-order LPF prototype will produce second-order BPF prototype.
84. IIR digital filter design using
MATLAB
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88. Reference
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1) Digital Signal Processing, Principle , Algorithm and Application, Forth
Edition, John G. Proakis Dimitris G.Manolakis (Chapter 9 &10)
2) https://ocw.mit.edu/resources/res-6-008-digital-signal-processing-spring-
2011/video-lectures/lecture-14-design-of-iir-digital-filters-part-
1/MITRES_6_008S11_lec14.pdf
Editor's Notes
A signal flow graph provides an alternative, but equivalent, graphical representation to a block diagram structure that we have been using to illustrate various system realizations.
The basic elements of a flow graph are branches and nodes. A signal flow graph is basically a set of directed branches that connect at nodes.
By definition, the signal out of a branch is equal to the branch gain (system function) times the signal into the branch.
Furthermore, the signal at a node of a flow is equal to the sum of signals from all branches connecting to the node.
The system block diagram can be converted to the signal flow graph shown figure above . We note that the flow graph contains five nodes labeled 1 through 5. Two of the nodes (1,3) are summing nodes, while the other three nodes represent branching points. Branch transmittances are indicated for the branches in the flow graph. Note that a delay is indicated by the branch transmittance z-1. when the branch transmittance is unity , it is left unlabeled. The input to the system originates at a source node and the output signal is extracted at sink node.
We observe that the transposed direct form II structure requires the same numbers of multiplications, additions, and memory locations as the original direct-form II structure.
A parallel-form realization of an IIR System can be obtained by performing a partial fraction expansion of H(z). Without loss of generality, we gain assume that N>= M and that the poles are distinct. Then, by performing a partial- fraction expansion of H(z), we obtain the result
In general, some of the poles of H(z) may be complex valued. In such a case, the corresponding coefficients Ak are also complex valued. To avoid multiplications by complex numbers, we can combine pairs of complex-conjugate poles to form two-pole subsystem. In addition, we combine, in an arbitrary manner, pairs of real-valued poles to form two-pole subsystem. Each of these subsystems has the form
In the design of IIR filters, we shall specify the desired filter characteristics for the magnitude response only, this does not mean that we consider the phase response unimportant. Since the magnitude and phase characteristics are related, we specify the desired magnitude characteristics and accept the phase response that is obtained from the design methodology
In the design of IIR filters, we shall specify the desired filter characteristics for the magnitude response only, this does not mean that we consider the phase response unimportant. Since the magnitude and phase characteristics are related, we specify the desired magnitude characteristics and accept the phase response that is obtained from the design methodology
This method inappropriate for designing highpass filters due to the spectrum aliasing that results from the sampling process