* New Approach to Observer-Based Finite-Time H∞ Control of Discrete-Time One-Sided Lipschitz Systems with Uncertainties
* Deploying a Deep Learning-based Application for an Efficient Thermal Energy Storage Air-Conditioning (TES-AC) System: Design Guidelines
* Monitoring Heart Rate Variability Based on Self-powered ECG Sensor Tag
A delay decomposition approach to robust stability analysis of uncertain syst...ISA Interchange
This document presents a delay decomposition approach to robust stability analysis of uncertain systems with time-varying delay. It proposes new robust stability criteria for such systems based on Lyapunov stability methods. The criteria are provided in terms of linear matrix inequalities that can be solved efficiently via optimization algorithms. The approach avoids using bounding techniques and model transformations that typically introduce conservatism. Numerical examples demonstrate the proposed method provides less conservative results than existing approaches.
● Non-fragile Dynamic Output Feedback H∞ Control for a Class of Uncertain Switched Systems with Time-varying Delay
● An Integrated Emergency Response Tool for Developing Countries: Case of Uganda
● Study the Multiplication M-sequences and Its Reciprocal Sequences
● Wireless Power Transfer for 6G Network Using Monolithic Components on GaN
● Circular Ribbon Antenna Array Design For Imaging Application
Stability and stabilization of discrete-time systems with time-delay via Lyap...IJERA Editor
The stability and stabilization problems for discrete systems with time-delay are discussed .The stability and
stabilization criterion are expressed in the form of linear matrix inequalities (LMI). An effective method
allowing us transforming a bilinear matrix Inequality (BMI) to a linear matrix Inequality (LMI) is developed.
Based on these conditions, a state feedback controller with gain is designed. An illustrative numerical example
is provided to show the effectiveness of the proposed method and the reliability of the results.
FEEDBACK LINEARIZATION AND BACKSTEPPING CONTROLLERS FOR COUPLED TANKSieijjournal
This paper investigates the usage of some sophisticated and advanced nonlinear control algorithms in order to control a nonlinear Coupled Tanks System. The first control procedure is called the Feedback linearisation control (FLC), this type of control has been found a successful in achieving a global exponential asymptotic stability, with very short time response, no significant overshooting is recorded and with a negligible norm of the error. The second control procedure is the approaches of Back stepping control (BC) which is a recursive procedure that interlaces the choice of a Lyapunov function with the design of feedback control, from simulation results it shown that this method preserves tracking, robust control and it can often solve stabilization problems with less restrictive conditions may been countered in other methods. Finally both of the proposed control schemes guarantee the asymptoticstability of the closed loop system meeting trajectory tracking objectives.
Feedback linearization and Backstepping controllers for Coupled Tanksieijjournal
This paper investigates the usage of some sophisticated and advanced nonlinear control algorithms inorder
to control a nonlinear Coupled Tanks System. The first control procedure is called the
Feedbacklinearisation control (FLC), this type of control has been found a successful in achieving a global
exponentialasymptotic stability, with very short time response, no significant overshooting is recordedand with a negligible norm of the error. The second control procedure is the approaches of Backsteppingcontrol (BC) which is a recursive procedure that interlaces the choice of a Lyapunov functionwith the design of feedback control, from simulation results it shown that this method preserves tracking, robust control and it can often solve stabilization problems with less restrictive conditions may beencountered in other methods. Finally both of the proposed control schemes guarantee theasymptoticstability of the closed loop system meeting trajectory tracking objectives
FEEDBACK LINEARIZATION AND BACKSTEPPING CONTROLLERS FOR COUPLED TANKSieijjournal
This paper investigates the usage of some sophisticated and advanced nonlinear control algorithms inorder to control a nonlinear Coupled Tanks System. The first control procedure is called the Feedbacklinearisation control (FLC), this type of control has been found a successful in achieving a global exponentialasymptotic stability, with very short time response, no significant overshooting is recordedand with a negligible norm of the error. The second control procedure is the approaches of Backsteppingcontrol (BC) which is a recursive procedure that interlaces the choice of a Lyapunov functionwith the design of feedback control, from simulation results it shown that this method preserves tracking, robust control and it can often solve stabilization problems with less restrictive conditions may beencountered in other methods. Finally both of the proposed control schemes guarantee the asymptoticstability of the closed loop system meeting trajectory tracking objectives.
Robust Exponential Stabilization for a Class of Uncertain Systems via a Singl...ijtsrd
In this paper, the robust stabilization for a class of uncertain chaotic or non chaotic systems with single input is investigated. Based on Lyapunov like Theorem with differential and integral inequalities, a simple linear control is developed to realize the global exponential stabilization of such uncertain systems. In addition, the guaranteed exponential convergence rate can be correctly estimated. Finally, some numerical simulations with circuit realization are provided to show the effectiveness of the obtained result. Yeong-Jeu Sun "Robust Exponential Stabilization for a Class of Uncertain Systems via a Single Input Control and its Circuit Implementation" Published in International Journal of Trend in Scientific Research and Development (ijtsrd), ISSN: 2456-6470, Volume-3 | Issue-6 , October 2019, URL: https://www.ijtsrd.com/papers/ijtsrd29322.pdf Paper URL: https://www.ijtsrd.com/engineering/electrical-engineering/29322/robust-exponential-stabilization-for-a-class-of-uncertain-systems-via-a-single-input-control-and-its-circuit-implementation/yeong-jeu-sun
Control theorists have extensively studied stability
as well as relative stability of LTI systems. In this research
paper we attempt to answer the question. How unstable is an
unstable system? In that effort we define instability exponents
dealing with the impulse response. Using these instability
exponents, we characterize unstable systems.
A delay decomposition approach to robust stability analysis of uncertain syst...ISA Interchange
This document presents a delay decomposition approach to robust stability analysis of uncertain systems with time-varying delay. It proposes new robust stability criteria for such systems based on Lyapunov stability methods. The criteria are provided in terms of linear matrix inequalities that can be solved efficiently via optimization algorithms. The approach avoids using bounding techniques and model transformations that typically introduce conservatism. Numerical examples demonstrate the proposed method provides less conservative results than existing approaches.
● Non-fragile Dynamic Output Feedback H∞ Control for a Class of Uncertain Switched Systems with Time-varying Delay
● An Integrated Emergency Response Tool for Developing Countries: Case of Uganda
● Study the Multiplication M-sequences and Its Reciprocal Sequences
● Wireless Power Transfer for 6G Network Using Monolithic Components on GaN
● Circular Ribbon Antenna Array Design For Imaging Application
Stability and stabilization of discrete-time systems with time-delay via Lyap...IJERA Editor
The stability and stabilization problems for discrete systems with time-delay are discussed .The stability and
stabilization criterion are expressed in the form of linear matrix inequalities (LMI). An effective method
allowing us transforming a bilinear matrix Inequality (BMI) to a linear matrix Inequality (LMI) is developed.
Based on these conditions, a state feedback controller with gain is designed. An illustrative numerical example
is provided to show the effectiveness of the proposed method and the reliability of the results.
FEEDBACK LINEARIZATION AND BACKSTEPPING CONTROLLERS FOR COUPLED TANKSieijjournal
This paper investigates the usage of some sophisticated and advanced nonlinear control algorithms in order to control a nonlinear Coupled Tanks System. The first control procedure is called the Feedback linearisation control (FLC), this type of control has been found a successful in achieving a global exponential asymptotic stability, with very short time response, no significant overshooting is recorded and with a negligible norm of the error. The second control procedure is the approaches of Back stepping control (BC) which is a recursive procedure that interlaces the choice of a Lyapunov function with the design of feedback control, from simulation results it shown that this method preserves tracking, robust control and it can often solve stabilization problems with less restrictive conditions may been countered in other methods. Finally both of the proposed control schemes guarantee the asymptoticstability of the closed loop system meeting trajectory tracking objectives.
Feedback linearization and Backstepping controllers for Coupled Tanksieijjournal
This paper investigates the usage of some sophisticated and advanced nonlinear control algorithms inorder
to control a nonlinear Coupled Tanks System. The first control procedure is called the
Feedbacklinearisation control (FLC), this type of control has been found a successful in achieving a global
exponentialasymptotic stability, with very short time response, no significant overshooting is recordedand with a negligible norm of the error. The second control procedure is the approaches of Backsteppingcontrol (BC) which is a recursive procedure that interlaces the choice of a Lyapunov functionwith the design of feedback control, from simulation results it shown that this method preserves tracking, robust control and it can often solve stabilization problems with less restrictive conditions may beencountered in other methods. Finally both of the proposed control schemes guarantee theasymptoticstability of the closed loop system meeting trajectory tracking objectives
FEEDBACK LINEARIZATION AND BACKSTEPPING CONTROLLERS FOR COUPLED TANKSieijjournal
This paper investigates the usage of some sophisticated and advanced nonlinear control algorithms inorder to control a nonlinear Coupled Tanks System. The first control procedure is called the Feedbacklinearisation control (FLC), this type of control has been found a successful in achieving a global exponentialasymptotic stability, with very short time response, no significant overshooting is recordedand with a negligible norm of the error. The second control procedure is the approaches of Backsteppingcontrol (BC) which is a recursive procedure that interlaces the choice of a Lyapunov functionwith the design of feedback control, from simulation results it shown that this method preserves tracking, robust control and it can often solve stabilization problems with less restrictive conditions may beencountered in other methods. Finally both of the proposed control schemes guarantee the asymptoticstability of the closed loop system meeting trajectory tracking objectives.
Robust Exponential Stabilization for a Class of Uncertain Systems via a Singl...ijtsrd
In this paper, the robust stabilization for a class of uncertain chaotic or non chaotic systems with single input is investigated. Based on Lyapunov like Theorem with differential and integral inequalities, a simple linear control is developed to realize the global exponential stabilization of such uncertain systems. In addition, the guaranteed exponential convergence rate can be correctly estimated. Finally, some numerical simulations with circuit realization are provided to show the effectiveness of the obtained result. Yeong-Jeu Sun "Robust Exponential Stabilization for a Class of Uncertain Systems via a Single Input Control and its Circuit Implementation" Published in International Journal of Trend in Scientific Research and Development (ijtsrd), ISSN: 2456-6470, Volume-3 | Issue-6 , October 2019, URL: https://www.ijtsrd.com/papers/ijtsrd29322.pdf Paper URL: https://www.ijtsrd.com/engineering/electrical-engineering/29322/robust-exponential-stabilization-for-a-class-of-uncertain-systems-via-a-single-input-control-and-its-circuit-implementation/yeong-jeu-sun
Control theorists have extensively studied stability
as well as relative stability of LTI systems. In this research
paper we attempt to answer the question. How unstable is an
unstable system? In that effort we define instability exponents
dealing with the impulse response. Using these instability
exponents, we characterize unstable systems.
Global stabilization of a class of nonlinear system based on reduced order st...ijcisjournal
The problem of global stabilization for a class of nonlinear system is considered in this paper.The sufficient
condition of the global stabilization of this class of system is obtained by deducing thestabilization of itself
from the stabilization of its subsystems. This paper will come up with a designmethod of state feedback
control law to make this class of nonlinear system stable, and indicate the efficiency of the conclusion of
this paper via a series of examples and simulations at the end. Theresults presented in this paper improve
and generalize the corresponding results of recent works.
Piecewise controller design for affine fuzzy systemsISA Interchange
This document presents a new method for designing piecewise controllers for affine fuzzy systems using dilated linear matrix inequalities (LMIs). The method separates the system matrix from the Lyapunov matrix, allowing the controller parameters to be independent of the Lyapunov matrix. This leads to less conservative LMI characterizations and a wider applicability than existing methods. The results are also extended to H1 state feedback synthesis. Numerical examples illustrate the superiority of the new convex LMI approach over other techniques.
Piecewise Controller Design for Affine Fuzzy SystemsISA Interchange
This document presents a new method for designing piecewise state feedback controllers for affine fuzzy systems. The method uses dilated linear matrix inequalities (LMIs) to characterize the system in a way that separates the system matrix from the Lyapunov matrix. This allows the controller parameters to be independent of the Lyapunov matrix. The results provide less conservative LMI characterizations than existing methods and can be applied to more general systems. The method is also extended to H-infinity state feedback synthesis. Numerical examples demonstrate the effectiveness of the new approach.
Comparative Analysis of Different Numerical Methods of Solving First Order Di...ijtsrd
A mathematical equation which relates various function with its derivatives is known as a differential equation.. It is a well known and popular field of mathematics because of its vast application area to the real world problems such as mechanical vibrations, theory of heat transfer, electric circuits etc. In this paper, we compare some methods of solving differential equations in numerical analysis with classical method and see the accuracy level of the same. Which will helpful to the readers to understand the importance and usefulness of these methods. Chandrajeet Singh Yadav"Comparative Analysis of Different Numerical Methods of Solving First Order Differential Equation" Published in International Journal of Trend in Scientific Research and Development (ijtsrd), ISSN: 2456-6470, Volume-2 | Issue-4 , June 2018, URL: http://www.ijtsrd.com/papers/ijtsrd13045.pdf http://www.ijtsrd.com/mathemetics/applied-mathematics/13045/comparative-analysis-of-different-numerical-methods-of-solving-first-order-differential-equation/chandrajeet-singh-yadav
The dynamics of networks enables the function of a variety of systems we rely on every day, from gene regulation and metabolism in the cell to the distribution of electric power and communication of information. Understanding, steering and predicting the function of interacting nonlinear dynamical systems, in particular if they are externally driven out of equilibrium, relies on obtaining and evaluating suitable models, posing at least two major challenges. First, how can we extract key structural system features of networks if only time series data provide information about the dynamics of (some) units? Second, how can we characterize nonlinear responses of nonlinear multi-dimensional systems externally driven by fluctuations, and consequently, predict tipping points at which normal operational states may be lost? Here we report recent progress on nonlinear response theory extended to predict tipping points and on model-free inference of network structural features from observed dynamics.
Stability behavior of second order neutral impulsive stochastic differential...Editor IJCATR
In this article, we study the existence and asymptotic stability in pth moment of mild solutions to second order neutral stochastic partial differential equations with delay. Our method of investigating the stability of solutions is based on fixed point theorem and Lipchitz conditions being imposed.
Controller Design Based On Fuzzy Observers For T-S Fuzzy Bilinear Models ijctcm
This article is devoted to the design of a fuzzy-observer-based control for a class of nonlinear systems with bilinear terms. The class of systems considered is the Takagi-Sugeno (T-S) fuzzy bilinear model. A new procedure to design the observer-based fuzzy controller for this class of systems is proposed. The aim is to design the fuzzy controller and the fuzzy observer of the augmented system separately in order to guarantee that the error between the state and its estimation converges faster to zero. By using the Lyapunov function, sufficient conditions are derived such that the closed-loop system is globally asymptotically stable. Moreover, sufficient conditions for controller design based on state estimation for robust stabilization of TS FBS with parametric uncertainties is proposed. The observer and controller gains are obtained by solving some linear matrix inequalities (LMIs). An example is given to illustrate the effectiveness of the proposed approach.
The document discusses finite element analysis and provides information on various topics related to it. It begins by listing the three methods of engineering analysis as experimental, analytical, and numerical/approximate methods. It then defines key finite element concepts such as finite element, finite element analysis, common element types, nodes, discretization, and the three phases of finite element method. It also discusses structural and non-structural problems, common methods associated with finite element analysis such as force method and stiffness method, and why polynomials are commonly used for interpolation in finite element analysis.
Semi-global Leaderless Consensus with Input Saturation Constraints via Adapti...IJRES Journal
In this paper, the problems of semi-global leaderless consensus for continuous-time multi-agent
systems under input saturation restraints are investigated. We consider the leaderless consensus problems
under fixed undirected communication topology. New necessary synthesis conditions are established for
achieving semi-global leaderless consensus via the distributed adaptive protocols, which is designed by utilizing
low gain feedback tactics and the relative state measurements of the neighboring agents. Finally, simulation
results illustrate the theoretic developments.
GLOBAL CHAOS SYNCHRONIZATION OF HYPERCHAOTIC QI AND HYPERCHAOTIC JHA SYSTEMS ...ijistjournal
This paper derives new results for the global chaos synchronization of identical hyperchaotic Qi systems (2008), identical hyperchaotic Jha systems (2007) and non-identical hyperchaotic Qi and Jha systems. Active nonlinear control is the method adopted to achieve the complete synchronization of the identical and different hyperchaotic Qi and Jha systems. Our stability results derived in this paper are established using Lyapunov stability theory. Numerical simulations are shown to validate and illustrate the effectiveness of the synchronization results derived in this paper.
GLOBAL CHAOS SYNCHRONIZATION OF HYPERCHAOTIC QI AND HYPERCHAOTIC JHA SYSTEMS ...ijistjournal
1) The document describes using active nonlinear control to achieve global chaos synchronization between identical and non-identical hyperchaotic systems.
2) It specifically derives new results for synchronizing identical hyperchaotic Qi and Jha systems, as well as non-identical hyperchaotic Qi and Jha systems.
3) The synchronization is achieved through designing appropriate active nonlinear controllers and proving global exponential stability of the synchronization error dynamics using Lyapunov stability theory. Numerical simulations validate the theoretical results.
Newton method based iterative learning control for nonlinear systemsTian Lin
The document proposes a Newton-method based iterative learning control (ILC) method for nonlinear systems. It decomposes the nonlinear ILC problem into a sequence of linear time-varying ILC problems that can be solved using existing linear ILC algorithms. This approach converges semi-locally and avoids calculating inverse systems. The algorithm is demonstrated in a simulation of a single link manipulator model that successfully tracks the reference signal across trials. Future work aims to improve global convergence, stability, and monotonic convergence properties.
Invariant Manifolds, Passage through Resonance, Stability and a Computer Assi...Diego Tognola
1) The document is a dissertation submitted to ETH Zurich that studies invariant manifolds, passage through resonance, stability, and applies these concepts to a synchronous motor model.
2) It first develops theory for a general Hamiltonian system coupled to a linear system by weak periodic perturbations, showing the persistence of invariant manifolds. It then uses averaging techniques to analyze global dynamics, assuming a finite number of resonances.
3) It represents the reduced system in a way suitable for stability analysis, covering both non-degenerate and degenerate cases.
4) The second part applies these methods to explicitly model a miniature synchronous motor, analytically deriving approximations and numerically simulating and confirming the dynamics, showing approach
ACTIVE CONTROLLER DESIGN FOR THE HYBRID SYNCHRONIZATION OF HYPERCHAOTIC XU AN...Zac Darcy
The synchronization of chaotic systems treats a pair of chaotic systems, which are usually called as master
and slave systems. In the chaos synchronization problem, the goal of the design is to synchronize the states
of master and slave systems asymptotically. In the hybrid synchronization design of master and slave
systems, one part of the systems, viz. their odd states, are completely synchronized (CS), while the other
part, viz. their even states, are completely anti-synchronized (AS) so that CS and AS co-exist in the process
of synchronization. This research work deals with the hybrid synchronization of hyperchaotic Xi systems
(2009) and hyperchaotic Li systems (2005). The main results of this hybrid research work are established
with Lyapunov stability theory. MATLAB simulations of the hybrid synchronization results are shown for
the hyperchaotic Xu and Li systems.
This document provides an overview of econometrics and its application in economic research. It discusses key topics such as:
1. The history and development of econometrics, from linear regression to advanced dynamic models.
2. Statistical issues that can arise in regression like multicollinearity and heteroscedasticity.
3. Model building in econometrics, including partial adjustment models, vector error correction models, and panel data analysis.
4. Examples of econometric analyses using Indonesian economic data to examine relationships between variables like GDP, investment, taxes, and expenditures.
Simulation and stability analysis of neural network based control scheme for ...ISA Interchange
This paper proposes a new adaptive neural network based control scheme for switched linear systems with parametric uncertainty and external disturbance. A key feature of this scheme is that the prior information of the possible upper bound of the uncertainty is not required. A feedforward neural network is employed to learn this upper bound. The adaptive learning algorithm is derived from Lyapunov stability analysis so that the system response under arbitrary switching laws is guaranteed uniformly ultimately bounded. A comparative simulation study with robust controller given in [Zhang L, Lu Y, Chen Y, Mastorakis NE. Robust uniformly ultimate boundedness control for uncertain switched linear systems. Computers and Mathematics with Applications 2008; 56: 1709–14] is presented.
Adaptive Stabilization and Synchronization of Hyperchaotic QI SystemCSEIJJournal
The hyperchaotic Qi system (Chen, Yang, Qi and Yuan, 2007) is one of the important models of four-
dimensional hyperchaotic systems. This paper investigates the adaptive stabilization and synchronization
of hyperchaotic Qi system with unknown parameters. First, adaptive control laws are designed to
stabilize the hyperchaotic Qi system to its equilibrium point at the origin based on the adaptive control
theory and Lyapunov stability theory. Then adaptive control laws are derived to achieve global chaos
synchronization of identical hyperchaotic Qi systems with unknown parameters. Numerical simulations
are shown to demonstrate the effectiveness of the proposed adaptive stabilization and synchronization
schemes.
1) The document analyzes the boundedness and domain of attraction of a fractional-order wireless power transfer (WPT) system.
2) It establishes a fractional-order piecewise affine model of the WPT system and derives sufficient conditions for boundedness using Lyapunov functions and inequality techniques.
3) The results provide a way to estimate the domain of attraction of the fractional-order WPT system and systems with periodically intermittent control.
The numerical solution of Huxley equation by the use of two finite difference methods is done. The first one is the explicit scheme and the second one is the Crank-Nicholson scheme. The comparison between the two methods showed that the explicit scheme is easier and has faster convergence while the Crank-Nicholson scheme is more accurate. In addition, the stability analysis using Fourier (von Neumann) method of two schemes is investigated. The resulting analysis showed that the first scheme
is conditionally stable if, r ≤ 2 − aβ∆t , ∆t ≤ 2(∆x)2 and the second
scheme is unconditionally stable.
Stressed Coral Reef Identification Using Deep Learning CNN Techniques
The Application of Information Systems to Improve Ambulance Response Times in the UK
Practical Considerations for Implementing Adaptive Acoustic Noise Cancellation in Commercial Earbuds
Development of Technology and Equipment for Non-destructive Testing of Defects in Sewing Mandrels of a Three-roll Screw Mill 30-80
Control and Treatment of Bone Cancer: A Novel Theoretical Study
Enhancing Semantic Segmentation through Reinforced Active Learning: Combating Dataset Imbalances and Bolstering Annotation Efficiency
Snowfall Shift and Precipitation Variability over Sikkim Himalaya Attributed to Elevation-Dependent Warming
Spatial and Temporal Variation of Particulate Matter (PM10 and PM2.5) and Its Health Effects during the Haze Event in Malaysia
Problems and opportunities for biometeorological assessment of conditions cold season
Case Study of Coastal Fog Events in Senegal Using LIDAR Ceilometer
Assessing the Impact of Gas Flaring and Carbon Dioxide Emissions on Precipitation Patterns in the Niger Delta Region of Nigeria Using Geospatial Analysis
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The dynamics of networks enables the function of a variety of systems we rely on every day, from gene regulation and metabolism in the cell to the distribution of electric power and communication of information. Understanding, steering and predicting the function of interacting nonlinear dynamical systems, in particular if they are externally driven out of equilibrium, relies on obtaining and evaluating suitable models, posing at least two major challenges. First, how can we extract key structural system features of networks if only time series data provide information about the dynamics of (some) units? Second, how can we characterize nonlinear responses of nonlinear multi-dimensional systems externally driven by fluctuations, and consequently, predict tipping points at which normal operational states may be lost? Here we report recent progress on nonlinear response theory extended to predict tipping points and on model-free inference of network structural features from observed dynamics.
Stability behavior of second order neutral impulsive stochastic differential...Editor IJCATR
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Controller Design Based On Fuzzy Observers For T-S Fuzzy Bilinear Models ijctcm
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GLOBAL CHAOS SYNCHRONIZATION OF HYPERCHAOTIC QI AND HYPERCHAOTIC JHA SYSTEMS ...ijistjournal
This paper derives new results for the global chaos synchronization of identical hyperchaotic Qi systems (2008), identical hyperchaotic Jha systems (2007) and non-identical hyperchaotic Qi and Jha systems. Active nonlinear control is the method adopted to achieve the complete synchronization of the identical and different hyperchaotic Qi and Jha systems. Our stability results derived in this paper are established using Lyapunov stability theory. Numerical simulations are shown to validate and illustrate the effectiveness of the synchronization results derived in this paper.
GLOBAL CHAOS SYNCHRONIZATION OF HYPERCHAOTIC QI AND HYPERCHAOTIC JHA SYSTEMS ...ijistjournal
1) The document describes using active nonlinear control to achieve global chaos synchronization between identical and non-identical hyperchaotic systems.
2) It specifically derives new results for synchronizing identical hyperchaotic Qi and Jha systems, as well as non-identical hyperchaotic Qi and Jha systems.
3) The synchronization is achieved through designing appropriate active nonlinear controllers and proving global exponential stability of the synchronization error dynamics using Lyapunov stability theory. Numerical simulations validate the theoretical results.
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1) The document is a dissertation submitted to ETH Zurich that studies invariant manifolds, passage through resonance, stability, and applies these concepts to a synchronous motor model.
2) It first develops theory for a general Hamiltonian system coupled to a linear system by weak periodic perturbations, showing the persistence of invariant manifolds. It then uses averaging techniques to analyze global dynamics, assuming a finite number of resonances.
3) It represents the reduced system in a way suitable for stability analysis, covering both non-degenerate and degenerate cases.
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ACTIVE CONTROLLER DESIGN FOR THE HYBRID SYNCHRONIZATION OF HYPERCHAOTIC XU AN...Zac Darcy
The synchronization of chaotic systems treats a pair of chaotic systems, which are usually called as master
and slave systems. In the chaos synchronization problem, the goal of the design is to synchronize the states
of master and slave systems asymptotically. In the hybrid synchronization design of master and slave
systems, one part of the systems, viz. their odd states, are completely synchronized (CS), while the other
part, viz. their even states, are completely anti-synchronized (AS) so that CS and AS co-exist in the process
of synchronization. This research work deals with the hybrid synchronization of hyperchaotic Xi systems
(2009) and hyperchaotic Li systems (2005). The main results of this hybrid research work are established
with Lyapunov stability theory. MATLAB simulations of the hybrid synchronization results are shown for
the hyperchaotic Xu and Li systems.
This document provides an overview of econometrics and its application in economic research. It discusses key topics such as:
1. The history and development of econometrics, from linear regression to advanced dynamic models.
2. Statistical issues that can arise in regression like multicollinearity and heteroscedasticity.
3. Model building in econometrics, including partial adjustment models, vector error correction models, and panel data analysis.
4. Examples of econometric analyses using Indonesian economic data to examine relationships between variables like GDP, investment, taxes, and expenditures.
Simulation and stability analysis of neural network based control scheme for ...ISA Interchange
This paper proposes a new adaptive neural network based control scheme for switched linear systems with parametric uncertainty and external disturbance. A key feature of this scheme is that the prior information of the possible upper bound of the uncertainty is not required. A feedforward neural network is employed to learn this upper bound. The adaptive learning algorithm is derived from Lyapunov stability analysis so that the system response under arbitrary switching laws is guaranteed uniformly ultimately bounded. A comparative simulation study with robust controller given in [Zhang L, Lu Y, Chen Y, Mastorakis NE. Robust uniformly ultimate boundedness control for uncertain switched linear systems. Computers and Mathematics with Applications 2008; 56: 1709–14] is presented.
Adaptive Stabilization and Synchronization of Hyperchaotic QI SystemCSEIJJournal
The hyperchaotic Qi system (Chen, Yang, Qi and Yuan, 2007) is one of the important models of four-
dimensional hyperchaotic systems. This paper investigates the adaptive stabilization and synchronization
of hyperchaotic Qi system with unknown parameters. First, adaptive control laws are designed to
stabilize the hyperchaotic Qi system to its equilibrium point at the origin based on the adaptive control
theory and Lyapunov stability theory. Then adaptive control laws are derived to achieve global chaos
synchronization of identical hyperchaotic Qi systems with unknown parameters. Numerical simulations
are shown to demonstrate the effectiveness of the proposed adaptive stabilization and synchronization
schemes.
1) The document analyzes the boundedness and domain of attraction of a fractional-order wireless power transfer (WPT) system.
2) It establishes a fractional-order piecewise affine model of the WPT system and derives sufficient conditions for boundedness using Lyapunov functions and inequality techniques.
3) The results provide a way to estimate the domain of attraction of the fractional-order WPT system and systems with periodically intermittent control.
The numerical solution of Huxley equation by the use of two finite difference methods is done. The first one is the explicit scheme and the second one is the Crank-Nicholson scheme. The comparison between the two methods showed that the explicit scheme is easier and has faster convergence while the Crank-Nicholson scheme is more accurate. In addition, the stability analysis using Fourier (von Neumann) method of two schemes is investigated. The resulting analysis showed that the first scheme
is conditionally stable if, r ≤ 2 − aβ∆t , ∆t ≤ 2(∆x)2 and the second
scheme is unconditionally stable.
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Journal of Electronic & Information Systems | Vol.4, Iss.2 October 2022
1.
2. Editor-in-Chief
Prof. Xinggang Yan
Editorial Board Members
University of Kent, United Kingdom
Chong Huang, United States
Yoshifumi Manabe, Japan
Hao Xu, United States
Shicheng Guo, United States
Diego Real Mañez, Spain
Senthil Kumar Kumaraswamy, India
Santhan Kumar Cherukuri, India
Asit Kumar Gain, Australia
Sedigheh Ghofrani, Iran
Lianggui Liu, China
Saleh Mobayen, Iran
Ping Ding, China
Youqiao Ma, Canada
M.M. Kamruzzaman, Bangladesh
Seyed Saeid Moosavi Anchehpoli, Iran
Sayed Alireza Sadrossadat, Iran
Sasmita Mohapatra, India
Akram Sheikhi, Iran
Husam Abduldaem Mohammed, Iraq
Neelamadhab Padhy, India
Baofeng Ji, China
Maxim A. Dulebenets, United States
Jafar Ramadhan Mohammed, Iraq
Shitharth Selvarajan, India
Schekeb Fateh, Switzerland
Alexandre Jean Rene Serres, Brazil
Dadmehr Rahbari, Iran
Jun Shen, China
Yuan Tian, China
Abdollah Doosti-Aref, Iran
Fei Wang, China
Xiaofeng Yuan, China
Kamarulzaman Kamarudin, Malaysia
Tajudeen Olawale Olasupo, United States
Md. Mahbubur Rahman, Korea
Héctor F. Migallón, Spain
3. Volume 4 Issue 2 • October 2022 • ISSN 2661-3204 (Online)
Journal of
Electronic & Information
Systems
Editor-in-Chief
Prof. Xinggang Yan
4. Volume 4 | Issue 2 | October 2022 | Page1-29
Journal of Electronic & Information Systems
Contents
Articles
1 New Approach to Observer-Based Finite-Time H∞
Control of Discrete-Time One-Sided Lipschitz
Systems with Uncertainties
Xinyue Tang Yali Dong Meng Liu
10 Monitoring Heart Rate Variability Based on Self-powered ECG Sensor Tag
Nhat Minh Tran Ngoc-Giao Pham Thang Viet Tran
21 Deploying a Deep Learning-based Application for an Efficient Thermal Energy Storage Air-Condition-
ing (TES-AC) System: Design Guidelines
Mirza Rayana Sanzana Mostafa Osama Mostafa Abdulrazic Jing Ying Wong Chun-Chieh Yip
6. 2
Journal of Electronic & Information Systems | Volume 04 | Issue 02 | Special Issue | October 2022
be summed up as H∞ standard control problems: interfer-
ence suppression problem, tracking problem, and robust
stability problem. Because of its practical importance,
the H∞ control problem has always been an important
research topic. The main purpose of H∞ control is based
on reducing the influence of external disturbance input
on the adjustable output of the system. In order to ensure
the required robust stability, some results have been ob-
tained on the design of H∞ control [6-11]
. This control is
usually available on the assumption that the entire state is
accessible. However, in numerous cases, this assumption
is invalid, so it is very important to construct an observer
that can provide the estimated value of the system state [12]
.
In recent years, the observer-based control has attracted
the attention of researchers, and some results have been
obtained [13,14]
.
Moreover, in some practical cases, the system state
cannot exceed a defined boundary within a finite time in-
terval. Hence, the finite-time transient performance should
be considered. Recently, finite-time stability and H∞ con-
trol problems have gradually become a well-researched
topic and have been applied to many systems [15-18]
. In
2020, Wang J X et al. [15]
considered the problem of robust
finite-time stabilization for uncertain discrete-time linear
singular systems. Feng T et al. [16]
studied the problem of
finite time stability and stabilization for fractional-order
switched singular continuous-time system. Zhang T L
et al. [17]
looked at the finite-time stability and stabilization
for linear discrete stochastic systems.
However, so far, the problem of observer-based fi-
nite-time H∞ control for discrete-time one-sided Lipschitz
systems have not been fully addressed, which leads to the
main purpose of our research.
In this paper, the observer-based finite-time H∞ con-
troller for nonlinear discrete-time system with uncertain-
ties is studied. We design the observer and observer-based
controller. Using Lyapunov function approach and some
lemmas, we obtain the criterion of H∞ FTB for the closed-
loop system. Finally, the validity of the proposed method
is demonstrated by a numerical example.
This paper is organized as follows. Section 2 covers
some preliminary information as well as the problem
statement. In Section 3, the sufficient conditions of FTB
an H∞ FTB for nonlinear discrete-time systems are estab-
lished. In Section 4, a numerical example is presented.
Conclusions are given in Section 5.
Notations n
R denotes the n-dimensional Euclidean
space. ∗ denotes a block of symmetry. ( )
B B
< >
0 0 denotes
the matrix B is a negative definite (positive definite) sym-
metric matrix. We define ( ) T
He S =S S
+ . and
denotes the maximum eigenvalue and minimum eigen-
value of a matrix respectively. , is inner product in the
space n
R , i.e. given , n
x y R
∈ , then , T
x y x y
= . denotes the
non-negative integer set.
2. Problem Formulation
Consider the following uncertain one-sided Lipschitz
discrete-time system:
nonlinear discrete-time systems are established. In Section 4, a numerical example
Conclusions are given in Section 5.
Notations n
R denotes the n -dimensional Euclidean space. denote
symmetry. ( )
B B
0 0 denotes the matrix B is a negative definite (positive definit
matrix. We define ( ) T
He S =S S
. max ( )
λ and min ( )
λ denotes the maximum eig
minimum eigenvalue of a matrix respectively. , is inner product in the space R
, n
x y R
, then , T
x y x y
. denotes the non-negative integer set.
2. Problem Formulation
Consider the following uncertain one-sided Lipschitz discrete-time system:
1 ( Δ ( )) ( ) ,
( Δ ( )) ,
,
k k k k k
k k
k k k
x A A k x g x Bu w
y C C k x
z Ex Fw
(1)
where n
k
x R
is the n -dimensional state vector, l
k
y R
is the output measu
m
k
u R
is the control input. q
k
z R
is the control output. The disturbance p
k
w R
, .
N
T
k k
k
w w d d
2
0
0 (2)
, , ,
A B C E and F are known real constant matrices. Δ ( )
A k and Δ ( )
C k are
matrices, which are assumed to be of the form:
1 1 1 2 2 2
Δ ( ) Δ ( ) , Δ ( ) Δ ( ) ,
A k M k N C k M k N
(3)
where , ,
M M N
1 2 1 and 2
N are known real constant matrices, and Δ ( )( , )
i k i 1 2 are
time-varying matrix-valued function subject to the following conditions:
Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
(4)
( )
k
g x is a nonlinear function satisfying the following assumptions.
Assumption 1 [19]
( )
g x verifies the one-sided Lipschitz condition:
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
(5)
where ρ is the so-called one sided Lipschitz constant.
Assumption 2 [19]
( )
g x verifies the quadratic inner-bounded condition:
2 2
ˆ ˆ ˆ ˆ
( ) ( ) ( ) ( ), ,
ˆ
, ,
n
g x g x β x x α g x g x x x
x x R
(6)
where α and β are known constants.
Remark 1 Different from the traditional Lipschitz condition, constant ρ , α
nonlinearity considered here can be negative, positive or zero.
In this paper, we construct the following state observer-based controller:
1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
(7)
where ˆk
x is the estimate of ,
k
x K and L are the controller and observer gains, re
be designed.
Let ˆ .
k k k
e x x
Then we have:
(1)
where n
k
x R
∈ is the n-dimensional state vector, l
k
y R
∈ is the
output measurement, and m
k
u R
∈ is the control input. q
k
z R
∈
is the control output. The disturbance p
k
w R
∈ satisfies:
, .
N
T
k k
k
w w d d
=
≤ ≥
∑ 2
0
0 (2)
, , ,
A B C E and F are known real constant matrices.
nonlinear discrete-time systems are established. In Section 4, a numerical example i
Conclusions are given in Section 5.
Notations n
R denotes the n -dimensional Euclidean space. denotes
symmetry. ( )
B B
0 0 denotes the matrix B is a negative definite (positive definite
matrix. We define ( ) T
He S =S S
. max ( )
λ and min ( )
λ denotes the maximum eige
minimum eigenvalue of a matrix respectively. , is inner product in the space n
R
, n
x y R
, then , T
x y x y
. denotes the non-negative integer set.
2. Problem Formulation
Consider the following uncertain one-sided Lipschitz discrete-time system:
1 ( Δ ( )) ( ) ,
( Δ ( )) ,
,
k k k k k
k k
k k k
x A A k x g x Bu w
y C C k x
z Ex Fw
(1)
where n
k
x R
is the n -dimensional state vector, l
k
y R
is the output measur
m
k
u R
is the control input. q
k
z R
is the control output. The disturbance p
k
w R
s
, .
N
T
k k
k
w w d d
2
0
0 (2)
, , ,
A B C E and F are known real constant matrices. Δ ( )
A k and Δ ( )
C k are t
matrices, which are assumed to be of the form:
1 1 1 2 2 2
Δ ( ) Δ ( ) , Δ ( ) Δ ( ) ,
A k M k N C k M k N
(3)
where , ,
M M N
1 2 1 and 2
N are known real constant matrices, and Δ ( )( , )
i k i 1 2 are th
time-varying matrix-valued function subject to the following conditions:
Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
(4)
( )
k
g x is a nonlinear function satisfying the following assumptions.
Assumption 1 [19]
( )
g x verifies the one-sided Lipschitz condition:
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
(5)
where ρ is the so-called one sided Lipschitz constant.
Assumption 2 [19]
( )
g x verifies the quadratic inner-bounded condition:
2 2
ˆ ˆ ˆ ˆ
( ) ( ) ( ) ( ), ,
ˆ
, ,
n
g x g x β x x α g x g x x x
x x R
(6)
where α and β are known constants.
Remark 1 Different from the traditional Lipschitz condition, constant ρ , α a
nonlinearity considered here can be negative, positive or zero.
In this paper, we construct the following state observer-based controller:
1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
(7)
where ˆk
x is the estimate of ,
k
x K and L are the controller and observer gains, res
be designed.
Let ˆ .
k k k
e x x
Then we have:
and
nonlinear discrete-time systems are established. In Section 4, a numerical example is presented.
Conclusions are given in Section 5.
Notations n
R denotes the n -dimensional Euclidean space. denotes a block of
symmetry. ( )
B B
0 0 denotes the matrix B is a negative definite (positive definite) symmetric
matrix. We define ( ) T
He S =S S
. max ( )
λ and min ( )
λ denotes the maximum eigenvalue and
minimum eigenvalue of a matrix respectively. , is inner product in the space n
R , i.e. given
, n
x y R
, then , T
x y x y
. denotes the non-negative integer set.
2. Problem Formulation
Consider the following uncertain one-sided Lipschitz discrete-time system:
1 ( Δ ( )) ( ) ,
( Δ ( )) ,
,
k k k k k
k k
k k k
x A A k x g x Bu w
y C C k x
z Ex Fw
(1)
where n
k
x R
is the n -dimensional state vector, l
k
y R
is the output measurement, and
m
k
u R
is the control input. q
k
z R
is the control output. The disturbance p
k
w R
satisfies:
, .
N
T
k k
k
w w d d
2
0
0 (2)
, , ,
A B C E and F are known real constant matrices. Δ ( )
A k and Δ ( )
C k are time-varying
matrices, which are assumed to be of the form:
1 1 1 2 2 2
Δ ( ) Δ ( ) , Δ ( ) Δ ( ) ,
A k M k N C k M k N
(3)
where , ,
M M N
1 2 1 and 2
N are known real constant matrices, and Δ ( )( , )
i k i 1 2 are the unknown
time-varying matrix-valued function subject to the following conditions:
Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
(4)
( )
k
g x is a nonlinear function satisfying the following assumptions.
Assumption 1 [19]
( )
g x verifies the one-sided Lipschitz condition:
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
(5)
where ρ is the so-called one sided Lipschitz constant.
Assumption 2 [19]
( )
g x verifies the quadratic inner-bounded condition:
2 2
ˆ ˆ ˆ ˆ
( ) ( ) ( ) ( ), ,
ˆ
, ,
n
g x g x β x x α g x g x x x
x x R
(6)
where α and β are known constants.
Remark 1 Different from the traditional Lipschitz condition, constant ρ , α and β in the
nonlinearity considered here can be negative, positive or zero.
In this paper, we construct the following state observer-based controller:
1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
(7)
where ˆk
x is the estimate of ,
k
x K and L are the controller and observer gains, respectively, to
be designed.
Let ˆ .
k k k
e x x
Then we have:
are time-varying matrices, which are assumed
to be of the form:
nonlinear discrete-time systems are established. In Section 4, a numerica
Conclusions are given in Section 5.
Notations n
R denotes the n -dimensional Euclidean space.
symmetry. ( )
B B
0 0 denotes the matrix B is a negative definite (posit
matrix. We define ( ) T
He S =S S
. max ( )
λ and min ( )
λ denotes the ma
minimum eigenvalue of a matrix respectively. , is inner product in th
, n
x y R
, then , T
x y x y
. denotes the non-negative integer set.
2. Problem Formulation
Consider the following uncertain one-sided Lipschitz discrete-time
1 ( Δ ( )) ( ) ,
( Δ ( )) ,
,
k k k k k
k k
k k k
x A A k x g x Bu w
y C C k x
z Ex Fw
(1)
where n
k
x R
is the n -dimensional state vector, l
k
y R
is the ou
m
k
u R
is the control input. q
k
z R
is the control output. The disturbance
, .
N
T
k k
k
w w d d
2
0
0 (2)
, , ,
A B C E and F are known real constant matrices. Δ ( )
A k and Δ
matrices, which are assumed to be of the form:
1 1 1 2 2 2
Δ ( ) Δ ( ) , Δ ( ) Δ ( ) ,
A k M k N C k M k N
(3)
where , ,
M M N
1 2 1 and 2
N are known real constant matrices, and Δ ( )(
i k i
time-varying matrix-valued function subject to the following conditions:
Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
(4)
( )
k
g x is a nonlinear function satisfying the following assumption
Assumption 1 [19]
( )
g x verifies the one-sided Lipschitz condition
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
(5)
where ρ is the so-called one sided Lipschitz constant.
Assumption 2 [19]
( )
g x verifies the quadratic inner-bounded cond
2 2
ˆ ˆ ˆ ˆ
( ) ( ) ( ) ( ), ,
ˆ
, ,
n
g x g x β x x α g x g x x x
x x R
(6)
where α and β are known constants.
Remark 1 Different from the traditional Lipschitz condition, cons
nonlinearity considered here can be negative, positive or zero.
In this paper, we construct the following state observer-based cont
1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
(7)
where ˆk
x is the estimate of ,
k
x K and L are the controller and observe
be designed.
Let ˆ .
k k k
e x x
Then we have:
(3)
where , ,
M M N
1 2 1 and 2
N are known real constant matri-
ces, and
nonlinear discrete-time systems are established. In Section 4, a numerical example is presented.
Conclusions are given in Section 5.
Notations n
R denotes the n -dimensional Euclidean space. denotes a block of
symmetry. ( )
B B
0 0 denotes the matrix B is a negative definite (positive definite) symmetric
matrix. We define ( ) T
He S =S S
. max ( )
λ and min ( )
λ denotes the maximum eigenvalue and
minimum eigenvalue of a matrix respectively. , is inner product in the space n
R , i.e. given
, n
x y R
, then , T
x y x y
. denotes the non-negative integer set.
2. Problem Formulation
Consider the following uncertain one-sided Lipschitz discrete-time system:
1 ( Δ ( )) ( ) ,
( Δ ( )) ,
,
k k k k k
k k
k k k
x A A k x g x Bu w
y C C k x
z Ex Fw
(1)
where n
k
x R
is the n -dimensional state vector, l
k
y R
is the output measurement, and
m
k
u R
is the control input. q
k
z R
is the control output. The disturbance p
k
w R
satisfies:
, .
N
T
k k
k
w w d d
2
0
0 (2)
, , ,
A B C E and F are known real constant matrices. Δ ( )
A k and Δ ( )
C k are time-varying
matrices, which are assumed to be of the form:
1 1 1 2 2 2
Δ ( ) Δ ( ) , Δ ( ) Δ ( ) ,
A k M k N C k M k N
(3)
where , ,
M M N
1 2 1 and 2
N are known real constant matrices, and Δ ( )( , )
i k i 1 2 are the unknown
time-varying matrix-valued function subject to the following conditions:
Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
(4)
( )
k
g x is a nonlinear function satisfying the following assumptions.
Assumption 1 [19]
( )
g x verifies the one-sided Lipschitz condition:
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
(5)
where ρ is the so-called one sided Lipschitz constant.
Assumption 2 [19]
( )
g x verifies the quadratic inner-bounded condition:
2 2
ˆ ˆ ˆ ˆ
( ) ( ) ( ) ( ), ,
ˆ
, ,
n
g x g x β x x α g x g x x x
x x R
(6)
where α and β are known constants.
Remark 1 Different from the traditional Lipschitz condition, constant ρ , α and β in the
nonlinearity considered here can be negative, positive or zero.
In this paper, we construct the following state observer-based controller:
1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
(7)
where ˆk
x is the estimate of ,
k
x K and L are the controller and observer gains, respectively, to
be designed.
Let ˆ .
k k k
e x x
Then we have:
are the unknown time-varying ma-
trix-valued function subject to the following conditions:
The following amendments should be kindly made to our revision, with the proposed changes
are are highlighted in red.
1. In the title of the page 1, ‘Observer-based’ should be changed to ‘Observer-Based’.
2. In the right column of page 2, the formula n
R in row 2 is not aligned with its line.
3. In the same line (row 2, right column, on page 2), please change ‘¥’ to ‘¥’.
4. In the right column, Page 2, ‘ ( )
k
g x ’ in formula (1) should be ‘ ( )
k
g x ’
5. In the right column on Page 2 , formula (4) should have the following changes:
Wrong version: Δ ( )Δ ( ) , , , .
T
i i
k k I k
n
k
i
1 2
New version: Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
¥
6. In the right column on Page 2, the square 2 in formula (5) should not be italicized.
Change ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
To
2
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
n
g x g x x x ρ x x x x R
7. In the right column on page 2, in the third line in Remark 1, please change ‘ere’ to ‘here’
8. In the right column on page 2, formula (7) should be made the following changes:
Change 1
ˆ ( ) ( ),
ˆ ,
k k k
k k k
k k
x A g Bu L y C
K
x x
x
x
u
to 1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
9. The very beginning on of the left column on page 3, please change
ˆ
( , ) ( ) ( ).
k k k
k
g x x g x g x
to ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
10. Please change formula (9) in the left column on page 3 as follows:
Change
,
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A LC A LC
g x I
g x I
g x x
A
A
I
To
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
11. In the left column on page 3, formula (10) (i.e. the fourth line in Definition 1),
change
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx L
c k N
to
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
L
(4)
( )
k
g x is a nonlinear function satisfying the following
assumptions.
Assumption 1 [19]
( )
g x verifies the one-sided Lipschitz
condition:
The following amendments should be kindly made to our revision, with the proposed changes
are are highlighted in red.
1. In the title of the page 1, ‘Observer-based’ should be changed to ‘Observer-Based’.
2. In the right column of page 2, the formula n
R in row 2 is not aligned with its line.
3. In the same line (row 2, right column, on page 2), please change ‘¥’ to ‘¥’.
4. In the right column, Page 2, ‘ ( )
k
g x ’ in formula (1) should be ‘ ( )
k
g x ’
5. In the right column on Page 2 , formula (4) should have the following changes:
Wrong version: Δ ( )Δ ( ) , , , .
T
i i
k k I k
n
k
i
1 2
New version: Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
¥
6. In the right column on Page 2, the square 2 in formula (5) should not be italicized.
Change ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
To
2
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
n
g x g x x x ρ x x x x R
7. In the right column on page 2, in the third line in Remark 1, please change ‘ere’ to ‘here’
8. In the right column on page 2, formula (7) should be made the following changes:
Change 1
ˆ ( ) ( ),
ˆ ,
k k k
k k k
k k
x A g Bu L y C
K
x x
x
x
u
to 1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
9. The very beginning on of the left column on page 3, please change
ˆ
( , ) ( ) ( ).
k k k
k
g x x g x g x
to ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
10. Please change formula (9) in the left column on page 3 as follows:
Change
,
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A LC A LC
g x I
g x I
g x x
A
A
I
To
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
11. In the left column on page 3, formula (10) (i.e. the fourth line in Definition 1),
change
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx L
c k N
to
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
L
(5)
where is the so-called one sided Lipschitz constant.
Assumption 2 [19]
( )
g x verifies the quadratic in-
ner-bounded condition:
nonlinear discrete-time systems are established. In Section 4, a numerical exam
Conclusions are given in Section 5.
Notations n
R denotes the n -dimensional Euclidean space. den
symmetry. ( )
B B
0 0 denotes the matrix B is a negative definite (positive de
matrix. We define ( ) T
He S =S S
. max ( )
λ and min ( )
λ denotes the maximum
minimum eigenvalue of a matrix respectively. , is inner product in the spac
, n
x y R
, then , T
x y x y
. denotes the non-negative integer set.
2. Problem Formulation
Consider the following uncertain one-sided Lipschitz discrete-time syste
1 ( Δ ( )) ( ) ,
( Δ ( )) ,
,
k k k k k
k k
k k k
x A A k x g x Bu w
y C C k x
z Ex Fw
(1)
where n
k
x R
is the n -dimensional state vector, l
k
y R
is the output m
m
k
u R
is the control input. q
k
z R
is the control output. The disturbance k
w
, .
N
T
k k
k
w w d d
2
0
0 (2)
, , ,
A B C E and F are known real constant matrices. Δ ( )
A k and Δ ( )
C k
matrices, which are assumed to be of the form:
1 1 1 2 2 2
Δ ( ) Δ ( ) , Δ ( ) Δ ( ) ,
A k M k N C k M k N
(3)
where , ,
M M N
1 2 1 and 2
N are known real constant matrices, and Δ ( )( , )
i k i 1 2
time-varying matrix-valued function subject to the following conditions:
Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
(4)
( )
k
g x is a nonlinear function satisfying the following assumptions.
Assumption 1 [19]
( )
g x verifies the one-sided Lipschitz condition:
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
(5)
where ρ is the so-called one sided Lipschitz constant.
Assumption 2 [19]
( )
g x verifies the quadratic inner-bounded condition:
2 2
ˆ ˆ ˆ ˆ
( ) ( ) ( ) ( ), ,
ˆ
, ,
n
g x g x β x x α g x g x x x
x x R
(6)
where α and β are known constants.
Remark 1 Different from the traditional Lipschitz condition, constant ρ
nonlinearity considered here can be negative, positive or zero.
In this paper, we construct the following state observer-based controller:
1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
(7)
where ˆk
x is the estimate of ,
k
x K and L are the controller and observer gain
be designed.
Let ˆ .
k k k
e x x
Then we have:
(6)
where and are known constants.
Remark 1 Different from the traditional Lipschitz con-
dition, constant , and in the nonlinearity considered
here can be negative, positive or zero.
In this paper, we construct the following state observ-
er-based controller:
The following amendments should be kindly made to our revision, with the proposed chang
are are highlighted in red.
1. In the title of the page 1, ‘Observer-based’ should be changed to ‘Observer-Based’.
2. In the right column of page 2, the formula n
R in row 2 is not aligned with its line.
3. In the same line (row 2, right column, on page 2), please change ‘¥’ to ‘¥’.
4. In the right column, Page 2, ‘ ( )
k
g x ’ in formula (1) should be ‘ ( )
k
g x ’
5. In the right column on Page 2 , formula (4) should have the following changes:
Wrong version: Δ ( )Δ ( ) , , , .
T
i i
k k I k
n
k
i
1 2
New version: Δ ( )Δ ( ) , , , .
T
i i
k k I k i
1 2
¥
6. In the right column on Page 2, the square 2 in formula (5) should not be italicized.
Change ˆ ˆ ˆ ˆ
( ) ( ), , , ,
2 n
g x g x x x ρ x x x x R
To
2
ˆ ˆ ˆ ˆ
( ) ( ), , , ,
n
g x g x x x ρ x x x x R
7. In the right column on page 2, in the third line in Remark 1, please change ‘ere’ to ‘here
8. In the right column on page 2, formula (7) should be made the following changes:
Change 1
ˆ ( ) ( ),
ˆ ,
k k k
k k k
k k
x A g Bu L y C
K
x x
x
x
u
to 1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
9. The very beginning on of the left column on page 3, please change
ˆ
( , ) ( ) ( ).
k k k
k
g x x g x g x
to ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
10. Please change formula (9) in the left column on page 3 as follows:
Change
,
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A LC A LC
g x I
g x I
g x x
A
A
I
Δ
A A BK BK
(7)
where ˆk
x is the estimate of ,
k
x K and L are the control-
ler and observer gains, respectively, to be designed.
Let ˆ .
k k k
e x x
= − Then we have:
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
7. 3
Journal of Electronic Information Systems | Volume 04 | Issue 02 | Special Issue | October 2022
where
ˆ ,
k k
Kx
u
1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
e very beginning on of the left column on page 3, please change
) ( ) ( ).
k k
k
g x g x
to ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
ase change formula (9) in the left column on page 3 as follows:
ange
,
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A LC A LC
g x I
g x I
g x x
A
A
I
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
he left column on page 3, formula (10) (i.e. the fourth line in Definition 1),
nge
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx L
c k N
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
L
Let
T
T T
k k k
x x e .
= The closed-loop system can be writ-
ten as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
= + (8)
where,
ˆ ,
k k
Kx
u
to 1
ˆ ˆ ˆ ˆ
( ) ( ),
ˆ ,
k k k k k k
k k
x Ax g x Bu L y Cx
u Kx
9. The very beginning on of the left column on page 3, please change
ˆ
( , ) ( ) ( ).
k k k
k
g x x g x g x
to ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
10. Please change formula (9) in the left column on page 3 as follows:
Change
,
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A LC A LC
g x I
g x I
g x x
A
A
I
To
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
11. In the left column on page 3, formula (10) (i.e. the fourth line in Definition 1),
change
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx L
c k N
to
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
L
(9)
The following definitions and some useful lemmas are
introduced to establish our main results.
Definition 1 (FTB) The closed-loop system (8) is said
to be FTB with respect to ( , , , ),
c c N R
1 2 where c c
1 2
0 ,
,
R 0 if
to 1
ˆ ,
k k k k k k
k k
u Kx
9. The very beginning on of the left column on page 3, please change
ˆ
( , ) ( ) ( ).
k k k
k
g x x g x g x
to ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
10. Please change formula (9) in the left column on page 3 as follows:
Change
,
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A LC A LC
g x I
g x I
g x x
A
A
I
To
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
11. In the left column on page 3, formula (10) (i.e. the fourth line in Definition 1),
change
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx L
c k N
to
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
L (10)
Definition 2 ( H∞ FTB) The closed-loop system (8) is
said to be H∞ FTB with respect to
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
Lemma 1 [18]
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
, where
c c
1 2
0 , R 0, if the system (8) is FTB with respect to
( , , , )
c c N R
1 2 and under the zero-initial condition the follow-
ing condition is satisfied
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
(11)
where is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and
X3 , where T
X =X
1 1
, T
X =X
2 2 0, then we obtain that
T
X +X X X
−
1
1 3 2 3 0
T
X +X X X
−
1
1 3 2 3 0 if and only if .
T
X X
X X
−
1 3
3 2
0
Lemma 2 [10]
Let ,
D S and
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
be real matrices with ap-
propriate dimensions and
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
1 [18]
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
, the following inequal-
ity holds:
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
(12)
Lemma 3 [11]
For matrices
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
and
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
with appro-
priate dimensions and scalar , the following inequality
holds,
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
ˆ ˆ
, ) ( ) ( ).
k k k k
x x g x g x
et
T
T T
k k k
x x e .
The closed-loop system can be written as:
( ) ,
k k k
g x +Iw
(8)
Δ
,
Δ
( )
, .
ˆ
( , )
k
k k
A BK BK
A L C A LC
g x I
I
g x x I
(9)
he following definitions and some useful lemmas are introduced to establish our main
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
),
R where c c
1 2
0 , ,
R 0 if
1 2 , 1,2, , .
T
k k
c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
, )
R γ , where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
the zero-initial condition the following condition is satisfied
,
N
T
k k
k
γ w w
2
0
(11)
s a prescribed positive scalar.
emma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
emma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
the following inequality holds:
1
Δ .
T T T T
D DD ηS S
η
(12)
emma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
wing inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
owing conditions satisfied:
.
T T
T
+Λ Φ
Φ φΦ
3
0 (13)
al of this paper is to construct an observer-based controller such that the system (8)
B.
Results
if the following conditions satisfied:
1 1 1
ˆ
ˆ
( ) (Δ Δ ) ( , ) ,
k k k
k k k k k
e x x
A LC e A L C x g x x w
where ˆ ˆ
( , ) ( ) ( ).
k k k k
g x x g x g x
Let
T
T T
k k k
x x e .
The closed-loop system can be written as:
1 ( ) ,
k+ k k k
x Ax g x +Iw
(8)
where,
Δ
,
Δ Δ
( )
( ) , .
ˆ
( , )
k
k
k k
A A BK BK
A
A L C A LC
g x I
g x I
g x x I
(9)
The following definitions and some useful lemmas are introduced to establish our main
results.
Definition 1 (FTB) The closed-loop system (8) is said to be FTB with respect to
( , , , ),
c c N R
1 2
where c c
1 2
0 , ,
R 0 if
0 0 1 2 , 1,2, , .
T T
k k
x Rx c x Rx c k N
(10)
Definition 2 ( H FTB) The closed-loop system (8) is said to be H FTB with respect to
( , , , , )
c c N R γ
1 2
, where c c
1 2
0 , R 0 , if the system (8) is FTB with respect to ( , , , )
c c N R
1 2
and under the zero-initial condition the following condition is satisfied
,
N N
T T
k k k k
k k
z z γ w w
2
0 0
(11)
where γ is a prescribed positive scalar.
Lemma 1 [18]
Given constant matrices ,
X X
1 2 and X3 , where T
X =X
1 1
, T
X =X
2 2 0 , then
we obtain that T
X +X X X
1
1 3 2 3 0 if and only if .
T
X X
X X
1 3
3 2
0
Lemma 2 [10]
Let ,
D S and Δ be real matrices with appropriate dimensions and
Δ Δ ,
T
I
the following inequality holds:
1
ΔS Δ .
T T T T T
D S D DD ηS S
η
(12)
Lemma 3 [11]
For matrices , ,
Λ Λ Λ
1 2 3 and Φ with appropriate dimensions and scalar φ ,
the following inequality holds,
,
T T
Λ +Λ Λ Λ Λ
1 3 2 2 3 0
if the following conditions satisfied:
.
T T
T
Λ φΛ +Λ Φ
φΦ φΦ
1 2 3
0 (13)
The goal of this paper is to construct an observer-based controller such that the system (8)
is H FTB.
3. Main Results
(13)
The goal of this paper is to construct an observer-based
controller such that the system (8) is H∞ FTB.
3. Main Results
In this part, sufficient conditions for FTB and H∞ FTB
of the system (8) via observer-based controller are devel-
oped.
3.1 Finite-time Boundedness
For expression convenience, we denote,
In this part, sufficient conditions for FTB and H
FTB of the system (8) via o
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( ,
c c
1
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 sy
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
Furthermore, the controller gain is given by K Φ V
1
and observer gain is L P
Proof We first prove that the system (8) is FTB. So, we define the Lyapunov fu
candidate as:
Theorem 1 Under Assumptions 1 and 2, system (8) is
FTB with respect to ( , , , )
c c R N
1 2 , if there exist a known
scalar
In this part, sufficient conditions for FTB and H
FTB of the system (8) via o
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( ,
c c
1
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 sy
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
Furthermore, the controller gain is given by K Φ V
1
and observer gain is L P
Proof We first prove that the system (8) is FTB. So, we define the Lyapunov fu
candidate as:
, scalars
In this part, sufficient conditions for FTB and H
FTB of the system (8) via o
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( ,
c c
1 2
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 sym
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
Furthermore, the controller gain is given by K Φ V
1
and observer gain is L P
Proof We first prove that the system (8) is FTB. So, we define the Lyapunov fu
candidate as:
,
In this part, sufficient conditions for FTB and H
FTB of the system (8) via o
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( ,
c c
1 2
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 sym
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
Furthermore, the controller gain is given by K Φ V
1
and observer gain is L P
Proof We first prove that the system (8) is FTB. So, we define the Lyapunov fu
candidate as:
In this part, sufficient conditions for FTB and H
FTB of the system (8) via ob
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( , ,
c c
1 2
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 sym
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
Furthermore, the controller gain is given by K Φ V
1
and observer gain is L P
1
Proof We first prove that the system (8) is FTB. So, we define the Lyapunov fun
candidate as:
,
this part, sufficient conditions for FTB and H
FTB of the system (8) via observer-
troller are developed.
-time Boundedness
ression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
heorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( , , , )
c c R N
1 2
,
xist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 symmetric
, ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
) ,
λ c +λ d c λ
2
1 1 3 2 2 (14)
13 16 18
24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
Θ Θ Θ
Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
(15)
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
urthermore, the controller gain is given by K Φ V
1
and observer gain is L P Y
1
.
roof We first prove that the system (8) is FTB. So, we define the Lyapunov functional
as:
, symmetric matrices , ,
P Q
0 0 and matrices
In this part, sufficient conditions for FTB and H
FTB of the system (8) via observer-
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( , , , )
c c R N
1 2
,
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 symmetric
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
(15)
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
Furthermore, the controller gain is given by K Φ V
1
and observer gain is L P Y
1
.
Proof We first prove that the system (8) is FTB. So, we define the Lyapunov functional
candidate as:
such that the following inequalities hold:
In this part, sufficient conditions for FTB and H
FTB of th
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, ,
, ,
( ), ( ), (
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB wi
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following ineq
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
Furthermore, the controller gain is given by K Φ V
1
and obs
Proof We first prove that the system (8) is FTB. So, we defin
candidate as:
(14)
In this part, sufficient conditions for FTB and H
FTB
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min
, ,
, ,
( ), ( ),
θ ρε βε θ ε I αε I θ ρε
P R
θ ε I αε I P R
P
λ λ R PR λ λ R PR λ =λ
1 1 2 2 1 2 3 3
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FT
if there exist a known scalar φ , scalars μ 1 , , ,
ε ε ε
1 2 3
0 0
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
Furthermore, the controller gain is given by K Φ V
1
an
Proof We first prove that the system (8) is FTB. So, we
candidate as:
(15)
where
In this part, sufficient conditions for FTB and H
FTB of the system (8) via o
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with respect to ( ,
c c
1
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ,
ε
4 0 , ,
η η
1 2 sy
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequalities hold:
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(16)
Furthermore, the controller gain is given by K Φ V
1
and observer gain is L P
Proof We first prove that the system (8) is FTB. So, we define the Lyapunov fu
candidate as:
(16)
Furthermore, the controller gain is given by
In this part, sufficient conditions for FTB and H
FTB of the sys
based controller are developed.
3.1 Finite-time Boundedness
For expression convenience, we denote,
max min max
, , ,
, , ,
( ), ( ), ( ).
θ ρε βε θ ε I αε I θ ρε βε
P R
θ ε I αε I P R
P R
λ λ R PR λ λ R PR λ =λ Q
1 1 2 2 1 2 3 3 4
4 3 4
1 1 1 1
2 2 2 2
1 2 3
1 1
2 2
0 0
1 1
0 0
2 2
Theorem 1 Under Assumptions 1 and 2, system (8) is FTB with res
if there exist a known scalar φ , scalars μ 1 , , , ,
ε ε ε
1 2 3
0 0 0 ε
4 0
matrices , ,
P Q
0 0 and matrices , , ,
Y V Φ such that the following inequaliti
( ) ( ) ,
N
μ λ c +λ d c λ
2
1 1 3 2 2
1 (14)
11 13 16 18
22 24 26 27 28
33
44
55
66 68 69
77 79 710
88
99
1010
0 0 0 0 0 0
0 0 0 0
0 0 0 0 0 0
0 0 0 0 0
0 0 0
0 0
0
0 0
0
0,
Θ Θ Θ Θ
Θ Θ Θ Θ Θ
Θ P
Θ P
Θ P P
Θ Θ Θ
Θ Θ Θ
Θ
Θ
Θ
where
( ) ,
, , ,
( ) , ,
, , ,
, , ,
( ), , ,
, ,
T T
T T T T
T T
T T T T
Θ μ P θ I η N N η N N
Θ θ I Θ A P V B Θ V
Θ θ I μ P Θ θ I Θ V B
Θ A P C Y Θ V Θ ε I
Θ ε I Θ Q Θ P
Θ φ PB BΦ Θ PM Θ P
Θ PM Θ YM Θ φΦ φΦ
11 1 1 1 1 2 2 2
13 2 16 18
22 3 24 4 26
27 28 33 2
44 4 55 66
68 69 1 77
79 2 710 2 88
1
1
,
, .
T
Θ η I Θ η I
99 1 1010 2
(
Furthermore, the controller gain is given by K Φ V
1
and observer
Proof We first prove that the system (8) is FTB. So, we define the
candidate as:
and observer gain is L P Y
−
= 1
.
Proof We first prove that the system (8) is FTB. So, we
define the Lyapunov functional candidate as:
, .
T T
k k k k k
V x Px e Pe P
= + 0 (17)
Then, we have