Ahmed Abdelrehim
Abstract—This paper discusses the indirect space vector
modulation for a four-leg matrix converter. The four-leg matrix
converter has been proven to be a reliable, cost-effective, and
compact power electronic interface to supply unbalanced or
nonlinear loads. However, the added fourth leg has shifted the
inverter side modulation from simple two-dimension SVM into
complex three-dimension. This paper employs a new technique to
implement indirect 3D SVM in digital controllers with further
simplification in the modulation process. Moreover, Simulink
simulation using repetitive controller has been performed to
regulate the output voltage for 400 Hz Power supplies.
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Indirect 3D-Space Vector Modulation for a Matrix Converter
1. Engineering, Technology & Applied Science Research Vol. 8, No. 2, 2018, 2847-2852 2847
www.etasr.com Abdelrehim et al.: Indirect 3D-Space Vector Modulation for a Matrix Converter
Indirect 3D-Space Vector Modulation for a Matrix
Converter
Ahmed Abdelrehim
Department of Electrical Engineering
Alexandria University
Alexandria, Egypt
ahmed.abdelrehim@siemens.com
Mohamed El-Habrouk
Department of Electrical Engineering
Alexandria University
Alexandria, Egypt
eepgmme1@yahoo.com
Samir Deghedie Erfan
Department of Electrical Engineering
Alexandria University
Alexandria, Egypt
deghedie@gmail.com
Karim Hassan Youssef
Department of Electrical Engineering
Alexandria University
Alexandria, Egypt
khmyoussef@yahoo.com
Abstract—This paper discusses the indirect space vector
modulation for a four-leg matrix converter. The four-leg matrix
converter has been proven to be a reliable, cost-effective, and
compact power electronic interface to supply unbalanced or
nonlinear loads. However, the added fourth leg has shifted the
inverter side modulation from simple two-dimension SVM into
complex three-dimension. This paper employs a new technique to
implement indirect 3D SVM in digital controllers with further
simplification in the modulation process. Moreover, Simulink
simulation using repetitive controller has been performed to
regulate the output voltage for 400 Hz Power supplies.
Keywords-repetitive controller; 3D SVM; four-leg matrix
converter
I. INTRODUCTION
The matrix converter is a static and direct AC to AC
converter with unique features of unity input power factor, high
power to volume ratio, high reliability and MTBF factor which
has gained interest in applications aiming to produce a
realization of a compact three-phase drive for military,
industrial and aerospace systems [1-3]. Moreover, researchers
utilized the matrix converter as an electronic interface layer
between all resources (wind, solar, storage, etc.) of the energy
matrix model and as an electronic transformer competing with
the traditional magnetic transformer. The added fourth leg is
placed to provide a return path for the zero-sequence current
during unbalancing and add the capability of supplying
different connected single-phase loads. Four-leg converters
have a superior ability to produce balanced output voltage
waveform even under severely unbalanced load or non-linear
load conditions [4]. A four-leg matrix converter topology is
shown in Figure 1. This paper investigates the indirect space
vector modulation which decouples the modulation into two
stages (rectifier + inverter) without intermediate energy
storage. This decoupling is efficient and allows separate control
to each stage, while as there is no intermediate energy storage,
a proper synchronization between the two stages is mandatory
to fulfill the power balance equation as instantaneous input
power shall be equal to the instantaneous output power for the
load [5]. At high-frequency applications with precise control
requirements as for naval and aerospace applications where the
115V-400Hz system is commonly used, traditional controllers
have failed to achieve a proper regulation, due to the limited
bandwidth so the repetitive controller is introduced as an
optimum solution for this control problem [6].
II. MATRIX CONVERTER MODEL
Matrix converter can be represented mathematically by
matrix M and switches are identified as , where X is the
output phase, Y is the input phase and S is the linking switch
between input and output. Rectifier switches are numbered
from to while inverter side switches are numbered from
to . The rectifier is represented in Figure 1. Governing
equations are:
Vout=M*Vin (1)
Iout=MT
*Iin (2)
Vout=Mi*VDC (3)
VDC=MR*Vin (4)
Vout=Mi*MR*Vin (5)
where , , , , , , , and are
output voltage, input voltage, output current, input current, DC
intermediate voltage, inverter side switching matrix, rectifier
side switching matrix, matrix converter switching matrix and
transposed matrix converter switching matrix respectively.
and Mi are described by (6) and (7) respectively:
=
1 3 5
2 4 6
(6)
2. spl
rec
ach
out
ass
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rec
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Fig. 1.
M =
S7 S8
S9 S1
S11 S1
S13 S1
M equals to M
M =
S7 S8
S9 S10
S11 S12
S13 S14
Equation (8)
=
S1 ∗ S7 S2
S1 ∗ S9 S2
S1 ∗ S11 S2
S1 ∗ S13 S2
=
SaA SaB
SbA SbB
ScA ScB
SnA SnB
In Figure 1 v
The mathema
Fig. 2.
III. INDIREC
Indirect spac
litting the mo
ctifying stage
hieve decoupl
tput voltage
sumption of vi
Rectifying St
The main fu
ntrol on the d
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ctifying stage,
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Schematic of a f
8
10
12
14
Mi*MR:
8
0
2
4
*
S1 S3 S5
S2 S4 S6
can be further
∗ S8 S3 ∗ S7
∗ S10 S3 ∗ S9
∗ S12 S3 ∗ S11
∗ S14 S3 ∗ S13
SaC
SbC
ScC
SnC
voltages are: V
atical modelin
Mathematical
CT SPACE VECT
ce vector mod
odulation into
and the seco
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irtual DC link
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unction of the
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, only two sw
y & Applied Sci
four-leg direct ma
5
6
r synthesized i
7 S4 ∗ S8 S
S4 ∗ S10 S
1 S4 ∗ S12 S5
3 S3 ∗ S14 S5
=
V
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V
V
and V
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TOR MODULAT
dulation can b
o two stages,
ond is called
the input curr
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as shown in F
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virtual DC l
witches must b
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A
atrix converter
(7)
(8)
into
S5 ∗ S7 S6 ∗ S8
5 ∗ S9 S6 ∗ S10
5 ∗ S11 S6 ∗ S1
5 ∗ S13 S6 ∗ S1
(9)
V =
V
V
V
.
zed in Figure 2
rix converter
TION
be implement
the first is
inversion sta
rent control an
and based o
Figure 1.
age is to achi
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link voltage. I
be closed at a
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Abdelrehim et a
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al.: Indirect 3D
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Fig. 3. Ni
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c to αβ coord
gle by which w
nverter modul
mulation that sw
re is no nee
mmonly hap
dulations as sh
Fig
In Figure 4, θ
actual hexa
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no need to syn
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gure 5. Modula
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e displacemen
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018, 2847-2852
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switch and on
o avoid short c
one to six as sh
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wn in Figure 3
ine switching com
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rectifying sta
dination and c
we can define
lation requirem
witching one v
ed to synthes
ppens with
hown in Figur
g. 4. Synthesi
θc is the angle
agon sector,
0<mc<1. For
nthesize the re
d during ever
ation process
the time inte
been translated
he current sec
ne to six. To
and one of t
is to have uni
nt angle betwee
lement this, th
2
Modulation for
ne lower swi
circuit. The re
hown in Figure
to guarantee t
3.
mbinations for the
dulation
age works by
calculating th
e the working
ment, it has
vector per sect
size two vect
conventional
re 4.
is of reference cu
e of the refere
mc the cu
matrix conver
ference vector
ry sector dura
happens by as
erval of eve
d into a train
ctor, numbers
o achieve the
the most inter
ity power facto
en input curren
he reference s
2848
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itch can be c
ectifier switche
e 1. Nine switc
that no short c
e rectifying stage
transforming
he reference v
sector. For m
been approve
tor is sufficien
tors per secto
l rectifier
urrent
ence current w
urrent modul
rter, mc=1 and
r as just one v
ation as show
ssigning one a
ry sector. V
of pulses car
are represent
e second targ
resting featur
or at the input
nt and voltage
signal given t
verter
closed
es are
ching
circuit
input
vector
matrix
ed by
nt and
or as
SVM
within
lation
there
vector
wn in
active
Vector
rrying
ted in
get of
res of
t side.
shall
to the
3. mo
ins
mo
con
app
fun
out
add
the
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app
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coo
inv
the
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odulation proc
stead of the inp
Fig. 5.
Inversion st
odulation, and
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proach for th
nction of inve
tput voltage
ded fourth leg
e zero-sequenc
ree-phase syste
+ +
And the tra
plied as it ha
balanced syst
plied. Due to
utral current p
le of 3D SVM
gs.
+ +
Transformati
ordination du
version stage,
e same time in
verter with
mbinations ar
p or n for ea
rned on (posi
egative). If th
ordination, th
nventional SV
divided into
alog to secto
ism number m
ctor angle on α
Prism Identif
If
0<θ<60
60<θ<12
120<θ<1
180<θ<24
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cess has been
put phase curr
. Rectifying s
III. INV
tage is conce
d as this pa
will address
he four-leg
ersion stage i
under balanc
g is responsibl
ce component
em follows (10
=0
ansformation f
as happened
tem (10) is n
the unbalanc
passing throug
M to provide
≠ 0
ion to statio
ue to the zer
switches on th
n order to avo
eight switc
re sixteen. Sw
ach leg, where
tive) and n in
he sixteen-ve
he result is
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may be ident
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the
0 the
80 the
40 the
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taken from i
rent.
stage SVM vector
VERSION STAGE
erned with in
aper discusse
the 3D SVM
matrix conve
is to provide
ced and unba
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t during unbal
0).
from abc to
with the rect
no longer vali
cing of the sy
gh the system
accurate swit
onary frame
ro-sequence c
he same leg ca
oid short circu
ches, the p
itching combi
e p indicates
ndicates the l
ectors are rep
a 3D hexago
into prisms. T
Figures 6-7).
tion on conv
tified by defi
ion.
en P=1
en P=2
en P=3
en P=4
ience Research
A
input phase v
rs selection
E
nverter side
es four-leg m
M as a modu
erter. The pr
a control ove
alanced loads
ng a current pa
lance. The bal
(10
αβ coordinati
tifier stage. F
id and (11) is
ystem, there w
m and it is the
tching pulses
(11
happens into
component. I
an’t be turned
uit. For the fo
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the upper swi
lower switch
presented into
on and secto
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Abdelrehim et a
oltage
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matrix
ulation
rimary
er the
. The
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For an
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)
o αβγ
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o αβα
ors of
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erence
8. E
B.
and
imp
bes
thre
swi
Vol. 8, No. 2, 20
al.: Indirect 3D
240<θ<30
300<θ<36
Vectors are d
Each prism con
Fig. 6. 3D re
Fig.
Fig.
Switching Vec
As the referen
d tetrahedron
plemented by
side each tetr
ee switching v
itching vector
018, 2847-2852
D-Space Vector M
00 then
60 then
distributed into
ntains four act
epresentation of sw
7. Prisms ide
8. Vector dist
ctor Selection
nce vector loca
number, sel
choosing the n
rahedron[8, 9]
vectors, to ca
the reference
2
Modulation for
n P=5
n P=6, where θ
o each prism a
tive vectors.
witching vectors i
entification for 3D
tribution into each
ation is define
ection of sw
nearest referen
]. Each tetrah
alculate the du
e required volt
2849
r a Matrix Con
θ= tan
as shown in F
in αβγ coordinatio
D SVM
h prism
ed by prism nu
witching vecto
nce vectors lo
hedron consis
uty cycle for
tage is transfo
verter
Figure
on
umber
ors is
ocated
sts of
each
ormed
4. firs
sw
wh
the
and
ma
var
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po
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rep
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ma
val
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suc
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Th
op
sho
10
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st to αβγ coor
witching vector
V
V
V
= d
The duty cyc
d
d
d
= ∗ S
= 1
here S is the d
e reference vec
d d represents
atrix is depend
rying values
rahedron. S m
ssible coincid
VM code check
e current value
The rectifyin
mbers from 1
tive rectifier
ectifier matrix
arge of genera
presenting the
presented on
o matrices as i
atrix converter
Fig. 9. M
A Simulink
lidate the effe
rying types o
ccessfully va
rious scenario
he input and
eration. The s
own in Table
-26.
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d d
V
V
V
cles can be furt
∗
V
V
V
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Matrix converter
V. SIMUL
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alidated as w
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I. The simula
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2).
ther calculated
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3)T
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prisms and te
and tetrahedron
RIX CONVERTE
edicated to gen
numbers repre
d would be re
me time the in
series of num
e inverter swit
matrix) as we
us to find all p
ure is shown in
code generation f
LINK SIMULATI
was successf
matrix conver
proposed indi
well. Simulati
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forms ensured
s carried out u
ation results ar
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A
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(12
d as shown in
(13
(14
Vα-ref Vβ-ref Vδ-r
nt switching v
switching vec
ng vectors, so
elected prism
been done for
etrahedrons. Th
n number to e
ER
nerating a ser
esenting the c
epresented on
nversion stage
mbers from 1
tches that wou
ell. Multiplyin
possible switch
n Figure 9.
from Mi and MR
ION
fully develop
rter operation
irect 3D SVM
ion worked
balanced linear
d proper con
using the param
re shown in F
h V
Abdelrehim et a
ailable
2)
(13).
3)
4)
ref)T
is
vector,
ctor. S
it has
m and
r each
he 3D
extract
ries of
current
n
e is in
to 16,
uld be
ng the
hes for
ed to
under
M was
under
r load.
nverter
meters
igures
R
A.
Vol. 8, No. 2, 20
al.: Indirect 3D
Source sys
Load syst
Switching freq
Input filter
Output filter
Repetitive Contr
Tracking con
Unbalanced
Balanced l
Nonlinear l
Non-Linear L
Fig. 12. FF
018, 2847-2852
D-Space Vector M
TABLE I.
tem
em
quency
(LC)
r (LC)
roller Q(z)
ntroller
d load 5Ω
load
load
Load
Fig. 10. O
(a) P
(b) P
(c) P
(d) N
Fig. 11. O
FT analysis for ou
2
Modulation for
SYSTEM PARAM
440V
115V-
1280
56Ω/0.8m
180uH+70
1.72377
1.663
1.868
Ω+5.5mH, 10Ω+6
5Ω +5
3phase diode
Output voltage
Phase A
Phase B
Phase C
Neutral
Output current
utput phase voltag
2850
r a Matrix Con
METERS
V-60Hz
-400Hz
00Hz
mH/10uF
0uH/100uF
2 1
76 0.75754
3 0.9914
8 0.8735
6.2mH, 20Ω+7.5m
5.5 mH
e bridge +50Ω
ge (THD=3.3%)
verter
mH
5. B.
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Fig. 13.
Unbalanced
Fig. 17. Inp
ng, Technology
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FFT analysis fo
Fig. 14.
Load
Fig. 15.
(a) P
(b) P
(c) P
(d)
Fig. 16. O
put current multip
y & Applied Sci
or output current
Error signal
Output voltage
Phase A
Phase B
Phase C
Neutral
Output Currents
plied by factor 50
ience Research
A
(THD=1.8%)
and input voltage
h V
Abdelrehim et a
e
C.
Vol. 8, No. 2, 20
al.: Indirect 3D
Fig. 19.
Fig. 20. FF
Non Linear L
F
Fig. 22.
018, 2847-2852
D-Space Vector M
Fig. 18.
FFT analysis fo
FT analysis for ou
Load
Fig. 21. Output
FFT analysis fo
2
Modulation for
Error signal
or input current (T
utput phase voltag
t voltage 115V/40
or input current (T
2851
r a Matrix Con
THD=48%)
ge (THD=3.3%)
00H
THD=48%)
verter
6. mo
bee
con
lim
(11
con
eff
rep
vo
[1]
[2]
[3]
[4]
[5]
[6]
[7]
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Fig
Fig. 25. Inp
This paper
odulation for
en implement
ntroller was s
mited bandw
15V/400Hz).
nditions (bal
fectiveness o
petitive contro
ltage in an exc
P. Zanchetta,
Empringham, “
AC power s
Electronics Sp
16, 2005
C. Klumpner,
process of th
Electronics Sp
1083–1088, Ju
D. Casadei, G
torque control
Electronics, Vo
F. Yue, P. W. W
space vector m
Electronics Co
R. Zhang, Hig
unbalanced loa
State Universit
R. Cárdenasa,
control system
Electric Power
T. Friedli, J.
evaluation of t
back-to-back
Electronics, Vo
ng, Technology
r.com
Fig. 23.
. 24. Repetitive
put current multip
VI. C
introduced th
four-leg matri
ted and simu
selected to reg
width for
The simulat
anced, unbal
f the propos
oller showed t
cellent way.
REFE
J. C. Clare, P.
“Control Design
upply using ge
pecialists Confere
F. Blaabjerg, P
he matrix conve
ecialist Conferenc
une 17-21, 2001
G. Serra, A. Tani,
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Wheeler, N. Mas
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onference, PESC 2
gh performance p
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ty, 1998
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m for four-leg mat
r Systems Researc
W. Kolar, J. Ro
three-phase AC–A
converter system
ol. 59, No. 12, pp
y & Applied Sci
Output current
e controller outpu
plied by factor 50
CONCLUSION
he design of
ix converter, c
ulated in Sim
gulate the out
high-freque
tion results
lanced, nonlin
sed modulati
the ability to
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018, 2847-2852
D-Space Vector M
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