1. 3288 IEEE TRANSACTIONS ON PLASMA SCIENCE, VOL. 42, NO. 10, OCTOBER 2014
Analysis of HTEM Horn-Type Antenna for
High-Power Impulse Radiation Applications
Sachin Bhagwat Umbarkar, Harivittal A. Mangalvedekar, Member, IEEE, Sreedevi Bindu,
Archana Sharma, Purnamasi Chotelal Saroj, and Kailash Chandra Mittal
Abstract—High-power microwaves are generated using high
voltage (HV) pulses, which are generated using a Marx generator
connected to a peaking stage. The output of the peaking stage
is the input to the half transverse electromagnetic (HTEM)
horn-type antenna. This paper discusses the effect of isolation
distance between HV tapered arm and the grounded reflector on
the variation of characteristic impedance and gain with respect
to the length, flair angle, and tapering angle of the antenna.
This paper also discusses the radiation loss on the side and back
of antenna. An experiment has been described using an available
Marx generator and HTEM antenna. Using the experimental and
simulation results, the optimal design parameters of antenna are
obtained.
Index Terms—Antenna, pulse, radiation, transverse
electromagnetic (TEM).
I. INTRODUCTION
HIGH-POWER microwave (HPM) can be generated by
feeding a high voltage (HV) pulse with rise time in the
range of nano to subnanoseconds. The applications for such
HPM are target object detection, transient radar, mine clearing,
detection of crack on underground pipeline, electronic effects
testing, jamming, and so on are reported in [1]–[3].
A HPM system generally consists of HV low rise time pulse
generator, such as the Marx generator, magnetic compression
circuits, pulse forming network, and so on. The development
and analysis of pulse forming network-based Marx generator
using finite integration techniques for an antenna load is given
in [4]. The input pulse to an antenna should have low rise time
and therefore, the Marx output is connected to the peaking
stage. The peaking stage consists of a peaking capacitor and
peaking switch [5]. This low rise time HV pulse is then fed
to an antenna. A block diagram of a HPM generator and its
calibration is shown in Fig. 1.
Manuscript received December 18, 2013; revised February 28, 2014 and
March 31, 2014; accepted April 8, 2014. Date of publication May 12, 2014;
date of current version October 21, 2014. This work was supported in part
by the Board of Research in Nuclear Science and in part by the Centre
of Excellence, Control and Nonlinear Dynamic System, Veermata Jijabai
Technological Institute, Mumbai, India.
S. B. Umbarkar and H. A. Mangalvedekar are with the Department of
Electrical Engineering, Veermata Jijabai Technological Institute, Mumbai
400019, India (e-mail: sachin.b.umbarkar@gmail.com; hamangalvedhekar@
vjti.org.in).
S. Bindu is with the Father Conceicao Rodrigues Institute of Technology,
Navi Mumbai 400703, India (e-mail: bindubalu@rediffmail.com).
A. Sharma, P. C. Saroj, and K. C. Mittal are with Accelerator & Pulse Power
Division, Bhabha Atomic Research Centre, Mumbai 400085, India (e-mail:
arsharma@barc.gov.in; pcsaroj@yahoo.in; kcm@barc.gov.in).
Color versions of one or more of the figures in this paper are available
online at http://ieeexplore.ieee.org.
Digital Object Identifier 10.1109/TPS.2014.2320496
Fig. 1. Block diagram of HPM generator.
Fig. 2. HTEM horn antenna with flair angle α = 31°.
The current developed in the conducting arm of the antenna
gives rise to electromagnetic fields [6]. The reflector of the
antenna which is at the ground potential focuses and directs
the magnetic field. The geometric shape of an antenna affects
the field radiation pattern [7], [8]. The impedance of the
source, the antenna, and the free space decides the radiation
intensity and patterns. The approximate step response of TEM
horn antenna is reported in [9]. Intermediate and far field
calculation of a reflector antenna, energized by a hydrogen
spark-gap switched pulser is described in [10]. Lee et al. [11]
have carried out the design study of TEM horn antenna. They
have discussed the interdependency and variation of gain, with
respect to flair angle, tapering angle, characteristic impedance
of TEM horn antenna. A practical half TEM horn antenna is
shown in Fig. 2.
This paper has made an attempt to include the salient
features of the contributions given in [4]–[11]. The mathe-
matical formulation for the characteristics impedance reported
in [11] and [12] has been modified by considering the isolation
distance between HV tapered arm and the grounded reflector.
The variation of characteristic impedance and gain with respect
to the flair angle and tapering angle of the antenna has been
plotted by considering the isolation distance (feeding height).
This has been plotted for width/height ratio less than one and
greater than one. This paper has also estimated the radiation
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2. UMBARKAR et al.: ANALYSIS OF HTEM HORN-TYPE ANTENNA FOR HIGH-POWER IMPULSE RADIATION APPLICATIONS 3289
Fig. 3. Schematic of near field and far field region.
Fig. 4. Side view and top view of antenna.
intensity of half transverse electromagnetic (HTEM) antenna
at the side and back, in order to get a feel of radiation
loss.
To understand the design and analysis of the antenna, an
experiment was conducted using HV pulse generator having
an output pulse of rise time 6.0122 ns connected to a half
TEM horn antenna. The experimental results were used along
with FIT-based software (CST microwave studio) and the
optimum geometrical parameters of the antenna were obtained.
A comparison of the experimental results with simulation has
been shown.
The rest of this paper is organized as follows: 1) the details
of antenna parameter calculation are reported in Section II;
2) the experiment on HTEM antenna is reported in Section III;
3) Section IV compares the experimental and simulation
results; and 4) Section V investigates the optimum geometrical
values of the antenna using the simulation software so as to
obtain maximum gain.
II. ANTENNA PARAMETER CALCULATIONS
An antenna generally consists of a near and far field region
as shown in Fig. 3. The near field region is defined by the
spherical region whose radius is less than R
R =
2L2
ctr
(1)
where L is the total length of the reflector of the antenna,
tr is the rise time of the pulse, and c is speed of light. The
spherical region with radius greater than R is called as the far
field region [13].
The far field region calculations are given in [13]. The
antenna parameters, such as tapering angle (θa), aperture
height (a), flair angle (α), plate width (w), and arc curvature,
are shown in Fig. 4 (for 3-D view, refer Fig. 2).
The various optimal geometrical relationships are given in
(1)–(8) [8]
w = 2L tan(α/2) (2)
a = L sin θa (3)
w
a
=
2 tan(α/2)
sin θa
(4)
α = 2 arctan
w
2a
sin(θa) . (5)
The characteristic impedance (Zc) for w/a > 1 and w/a < 1
are given by (6) and (7), respectively [12]
Zc = 2 ×
377
(w/a) + 2
(6)
Zc = 2 × 138 × log
8
(w/a)
. (7)
It should be noted that w and a have to be chosen such that
Zc = 377 to match the output impedance of antenna to
characteristic impedance of free space.
The geometric impedance ( fg) is then obtained from Zc
and intrinsic impedance Z0 given by (8)
fg =
Zc
Z0
. (8)
Equations (2)–(8) are discussed in [8] and these formulas
need to be rewrite by considering the feeding height. If antenna
has feeding height (Hf ) then its aperture heights will be
a = Hf + L sin θa. (9)
Thus, (w/a) ratio will be
w
a
=
2L tan(α/2)
H f + L sin θa
(10)
α = 2 arctan
1
2L
w
a
(Hf + L sin(θa) . (11)
The characteristic impedance (Zc) for w/a > 1 and w/a < 1
are given by (12) and (13), respectively
Zc =
377(Hf + L sin(θa))
H f + L(sin(α/2) + sin(θa))
(12)
Zc = 2 × 138 × log
8(Hf + L sin θa)
2L sin(α/2)
. (13)
The variation of characteristic impedance for (w/a < 1)
and (w/a > 1) for Hf = 0.33 m, is shown in Figs. 5 and 6,
respectively.
The antenna has been modeled as a transmission line model
[14], [15] and the total radiated E field in bore-sight is
ETOT
y (r, t)=−
Vo
r
a
4πcfg
δ(t)−
c
2L
u(t)−u t−
2L
c
(14)
where r is bore sight distance and δ(t) is the delta function.
Equation (14) is now expressed in terms of tapering angle of
the antenna. Equations (3) and (14) gives
ETOT
y (r, θa, t)
=−
Vo
r
a
4πcfg
⎡
⎣δ(t)−
c sin θa
2a
⎡
⎣
u(t)−
u t− 2
c
a
sin θa
⎤
⎦
⎤
⎦. (15)

3. 3290 IEEE TRANSACTIONS ON PLASMA SCIENCE, VOL. 42, NO. 10, OCTOBER 2014
Fig. 5. Characteristics impedance, Zc, of the HTEM horn antenna as a
function of the angles α and θa for (w/a < 1).
Fig. 6. Characteristics impedance, Zc, of the HTEM horn antenna as a
function of the angles α and θa for (w/a > 1).
Equation (10) shows that the total radiated field depends on
θa, r, f g, and dV/dt. Equation (15) is modified to (17)
θa = sin−1
2
a
w
tan
α
2
(16)
ETOT
y (r, α, t)
= −
Vo
r
a
4πcfg
δ(t)−
c
w
tan(α/2)
u(t)−
u t− w
c
1
tan(α/2)
.
(17)
Orientation of antenna (refer Fig. 4) has tapered length along
z-axis and flared along y-axis. The magnetic vector potential
(Az) is given by
Az =
μL
4π
I t − r
c
r
cos θa cos α (18)
where μ and ε are the permeability and permittivity of free
space, I(t − r/c) is the retarded current for 0° < θa < 90°
and 0° < α < 90°.
Equations (15)–(18), relate the antenna geometric parameter
with the electromagnetic field parameters. Further Maxwell’s
equations and vector magnetic potential equations are used to
obtain the electric and magnetic field equations
Hφ =
μL cos θa cos α sin θ
4π
⎛
⎝
I t − r
c
rc
+
I t − r
c
r2
⎞
⎠ (19)
Fig. 7. Experimental setup.
Eθ =
L sin θ
4πε
⎛
⎝−
I t − r
c
rc2
+
I t − r
c
r2c
+
I t − r
c
r3
⎞
⎠ (20)
Er =
L cos θa sin α cos θ
2πε
⎛
⎝
I t − r
c
r2c
+
I t − r
c
r3
⎞
⎠. (21)
It can be seen from (19)–(21) that Er , Eθ , Hφ are functions
of L, r, α, θa, c, ε and other current related quantity. The gain
of antenna is equal to [r · Efar/V]peak [3].
III. EXPERIMENT
The half TEM antenna has L = 1.5 m, α = 31°,
θa = 30°, which corresponds to width w = 0.83 m, and
a = 1.08 m. It is located on the top of Marx generator at a
height of 1.85 m from the ground. The 20 stage, 64 J, 360 pF,
300 kV Marx generator along with the peaking stage, and
antenna are shown in Fig. 7. The input pulse applied to the
antenna was a pulse with 6.0122-ns rise time and half-width at
full-maximum (FWHM) 150 ns. This is the pulse output of the
Marx generator peaking stage. The experiment described was
conducted to understand the shortcomings of the design and
modify the antenna.
Voltage and current output waveform of the Marx generator
peaking stage is shown in Fig. 8. It is observed that the
output pulse has 264-kV peak voltage and 1.4-kA peak current.
In this experiment, the radiated magnetic field is measured by
PRODYNE magnetic field sensor model B-24 (R) at various
distances and angles from the antenna center.
A. Calculation of the Radiated Magnetic Field
The simplified mathematical equation reported in [20] for
magnetic field measurement is given in
Voscilloscope = Aeq ·
dB
dt
= sensor (Volt) (22)

4. UMBARKAR et al.: ANALYSIS OF HTEM HORN-TYPE ANTENNA FOR HIGH-POWER IMPULSE RADIATION APPLICATIONS 3291
Fig. 8. Output of 20 stages of the Marx generator with peaking stage
(FWHM: 150 ns, Vch: 24 kV, RL: 160 , time/div.: 100 ns, rise time: 3 ns).
Fig. 9. Observed radiated far field, measured at 15-m distance.
where VOscilloscope is the voltage measured on the oscilloscope,
and B is the magnetic flux density. The B-dot sensor (Model
No. B-24-R) has equivalent area (Aeq) = 9 × 10−6 m2.
B. Calculation of the Radiated Electric Field (E)
The relationship of electric field intensity and magnetic field
is given in
E ≈ cB(Volt/meter). (23)
This sensor is connected to the oscilloscope using Bayonet
Neill–Concelman shielding cable, to avoid introduction of
the external field effects. Experimental reading of radiated
field at the 15-m distance is shown in Fig. 9, which gives
the peak amplitude of electric field intensity (5 kV/m). The
antenna feeding pulse has rise time of 6.0122 ns and has peak
amplitude 264 kV. Thus, the maximum rate of rise of voltage
is (dV/dt) = (264 kV/6.0122 ns) = 4.391 × 1013 V/s
(r Efar)peak ∝ (dV/dt) (24)
where r is the bore-sight distance [3].
IV. COMPARISON OF EXPERIMENTAL RESULTS
WITH CST SIMULATION
The FIT software gives 3-D platforms for design and analy-
sis of high-frequency electromagnetic problems. The radiated
free space propagation of the pulse is calculated using transient
analysis solver [19]. The simulation is carried out for different
far field distances and azimuthal angles for the input feeding
Fig. 10. Marx generator output pulse with peaking capacitor.
Fig. 11. Radiated E-field (far field) at 15-m distance for 5-ns rise time input
pulse.
Fig. 12. Scaled up version of Fig. 11.
pulse shown in Fig. 10. This feeding pulse is obtained from
the experiment.
The radiated pulse measured at 15-m bore-sight distance
from the center is shown in Fig. 11. The scaled up version of
the Fig. 11 is shown in Fig. 12 to measure the rise time of
radiated pulse.
The simulated results have first spike of 5.0025-kV/m
amplitude with rise time of 1.84 ns and second spike of
2.9655-kV/m with rise time of 3.16 ns. The 16.7481-ns
delayed second spike is probably due to ground plate reflection
[17]. These two consecutive spikes correspond to the two
dominant frequencies of 32.8 and 81.9 MHz, which can be
observed from Fig. 13 [16], [18].
The experimental results and simulation results for the far
field with respect to azimuthal angle and bore-sight distance

5. 3292 IEEE TRANSACTIONS ON PLASMA SCIENCE, VOL. 42, NO. 10, OCTOBER 2014
Fig. 13. FFT of radiated E-far field for 5-ns rise time pulse at 15-m distance.
Fig. 14. Electric field variation in azimuthal direction.
Fig. 15. Electric field variation with respect to distance.
Fig. 16. Electric field variation with height from ground floor.
are plotted, as shown in Figs. 14 and 15. It is observed that
both the results match. The variation of electric field intensity
with azimuth angle at 15-m distance from HTEM horn and
1.85-m height from ground was recorded as shown in Fig. 16.
Fig. 17. Gaussian pulse with 1.44-ns rise time.
Fig. 18. [r · Efar/V]peak versus antenna length (L).
Fig. 19. [r · Efar/V]peak versus antenna tapering angle (θa) L = 4.5 m,
α = 31°.
V. INVESTIGATION OF HTEM ANTENNA USING CST-MS
It is observed that the gain of the antenna is only 0.3, which
could be improved. Equations (14)–(16) and [8] indicate that
the gain is equal to (r · Efar/V)peak of antenna depends on
the electrical length of antenna (L/λ) and antenna parameters.
To observe the variation of the gain with respect to the antenna
geometry simulation is carried out with a Gaussian input pulse
of tr = 1.44 ns as shown in Fig. 17. Fig. 18 shows the variation
of gain with respect to the length of antenna [8]. It is observed
that as length of antenna increases its gain improves. From
Fig. 18, it is observed that the gain is 0.489 at 4.5-m length
of the antenna. Then, from (2) and (3) width w = 2.4959 m
and height a = 2.25 m. The simulation also shows that loss of
radiation reduces from the back and sides of the antenna for
L ≥ 4.5 m. Similarly the gain for variation of θa, α, and tr
are shown in Figs. 19–21, respectively. It is observed that the
gain is 0.444 at θa and α = 25°. It is to be noted that for this
antenna the maximum gain will be 0.5 as reported in [16].
Thus, the simulation shows that the impulse generator-peaking

6. UMBARKAR et al.: ANALYSIS OF HTEM HORN-TYPE ANTENNA FOR HIGH-POWER IMPULSE RADIATION APPLICATIONS 3293
Fig. 20. [r · Efar/V]peak versus antenna flair angle (α) for L = 4.5 m,
θa = 25°.
Fig. 21. [r · Efar/V]peak versus rise time for L = 4.5 m, θa = 23°, α = 25°.
switch stage output rise time should be modified to 2 ns. The
antenna geometry should be L = 4.5 m, α = 25°, θa = 23°
to obtain an approx gain of 0.5.
VI. CONCLUSION
This paper discusses the salient features of HTEM antenna.
It has modified the existing mathematical formula to include
the isolation distance between HV input arms and the
grounded reflector. The variation of characteristic impedance
with respect to flair angle and tapering angle have been
discussed. The variation of gain for the length, flair angle and
tapering angle of antenna, and rise time has been plotted. The
effects of side and back radiations have also been discussed.
An experiment has been conducted and it has been shown that
the experimental and simulations results match. The simulation
has been used to obtain the parameters of antenna, which can
give optimum gain value of 0.5 pu for the antenna.
ACKNOWLEDGMENT
The authors would like to thank Prof. O. G. Kakde
(Director-VJTI), Dr. L. M. Gantayet (Group Director-BARC),
Dr. N. M. Singh, Dr. W. Sushma, Prof. F. S. Kazi,
Dr. R N. Awale, and D. Aniket of VJTI, Mumbai, and
S. Singh, Dr. A. K. Ray, D. P. Chakravarthy, S. Sandip,
A. Ritu, T. Somesh, and C. S. Reddy, of BARC, Mumbai and
H. Singh of Onus Engineering Group, for their encouragement
and fabrication support.
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Sachin Bhagwat Umbarkar received the B.E.
degree in electronics and telecommunication from
Pravara Engineering College, University of Pune,
Pune, India, in 2009, and the M.Tech. degree from
the Veermata Jijabai Technological Institute (VJTI),
Mumbai, India, in 2011, where he is currently pur-
suing the Ph.D. degree in high-power microwave
application for UWB systems with the Electrical
Engineering Department.
He is currently a Research Fellow at VJTI.

7. 3294 IEEE TRANSACTIONS ON PLASMA SCIENCE, VOL. 42, NO. 10, OCTOBER 2014
Harivittal A. Mangalvedekar (M’14) received the
B.E., M.E., and Ph.D. degrees in electrical engineer-
ing from University of Mumbai, Mumbai, India, in
1979, 1984, and 1995, respectively.
He has been with the Veermata Jijabai Tech-
nological Institute (VJTI), Mumbai, India, for the
last 27 years, where he is currently a Professor
with the Electrical Engineering Department. He has
developed the High Voltage Laboratory at VJTI.
His current research interests include pulsed power
systems, and high-voltage and power systems
Sreedevi Bindu was born in Kerala, India, in 1970.
She received the Degree in electrical and electronics
engineering and the master’s degree in power system
from the University of Mumbai, Mumbai, India, in
1992 and 2001, respectively, where she is currently
pursuing the Ph.D. degree with the Department of
Electrical Engineering, Veermata Jijabai Technolog-
ical Institute.
She is an Associate Professor with the Fr. Conce-
icao Rodrigues Institute of Technology, Navi Mum-
bai, India.
Archana Sharma received the B.E. degree in
electrical engineering from Regional Engineering
College, Bhopal, India, in 1987, and the M.Sc.
(Eng.) and Ph.D. degrees from the Indian Institute
of Science Bangalore, India, in 1994 and 2003,
respectively. Her specialization is in the design and
development of single shot and repetitive pulsed
electron beam generators based on Marx generator
and linear induction accelerators.
She joined the Bhabha Atomic Research Center,
Mumbai, India, as a Scientific Officer, where she
is currently the Head of the Energetics and Pulsed Power Systems Section
with the Accelerator and Pulse Power Division. Her current research inter-
ests include compact pulsed power systems for HPM, FXR, and industrial
applications.
Purnamasi Chotelal Saroj was born in Uttar
Pradesh, India, in 1966. He received the Diploma
degree in industrial electronics and the B.E. degree
in electrical engineering from University of Mumbai,
Mumbai, India, in 1992.
He is currently with the Accelerator and Pulse
Power Division, Bhabha Atomic Research Center,
Mumbai. His current research interests include the
development of high-voltage pulse.
Mr. Saroj is a member of VEDA Society in India.
Kailash Chandra Mittal received the M.Sc. (Hons.)
degree in physics from Punjab University, Chandi-
garh, India, in 1974, and the Ph.D. degree in physics
from the University of Mumbai, Mumbai, India,
in 1986.
He joined the Plasma Physics Division at the
Bhabha Atomic Research Center, Mumbai, as a
Scientific Officer, in 1975. From 1989 to 1991, he
was with Cornell University, Ithaca, NY, USA, as a
Post Doctoral Fellow, the University of New Mex-
ico, Albuquerque, NM, USA, as a Senior Research
Associate, and the University of Paris, Paris, France, as an Invited Professor.
In 2007, he was with Ecole Polytechnique, Paris, as an INSA Fellow. He has
been involved in high-power electron beam generation and its applications to
flash X-ray generation, high-power microwave generation, and pulse neutron
generation for strategic purposes. He is involved in the Industrial Electron
Accelerator Program, where high-power electron beams are employed for
the industrial applications. He is currently involved in the development
of superconducting RF cavities for high-energy proton accelerators. He is
currently the Head of the Accelerator and Pulse Power Division, the Head
of the Particle Beam Generation and Diagnostics Section, and the Project
Manager of the Electron Beam Center. He has more than 175 scientific
publications/presentations in international/national journals/conferences.